Power conversion apparatus, power conversion method, motor system, and three-phase motor

The present invention relates generally to a power conversion apparatus and a power conversion method, and particularly to a technique of converting single-phase AC power into three-phase AC power and a three-phase motor driven by three-phase AC power obtained by converting single-phase AC power using such a technique.

Conventionally, power conversion apparatuses including a matrix converter have been in practical use (see Patent Literature (PTL) 1 and PTL 2, for example).

FIG. 20 is a circuit diagram of a matrix converter 200 disclosed in PTL 1. To drive a three-phase motor 203 using a single-phase AC power supply 201 , the matrix converter 200 directly converts an input AC voltage supplied from the single-phase AC power supply 201 into a three-phase output AC voltage using bidirectional switches 202 a to 202 f , and supplies the output AC voltage of each phase to a winding of a corresponding phase of the three-phase motor 203 .

Each of the bidirectional switches 202 a to 202 f includes two switching elements connected in inverse parallel, each capable of changing between a unidirectional conducting state and a non-conducting state. A magnitude determining unit 204 determines the magnitude relationship between the voltages at the terminals of the single-phase AC power supply 201 . According to the magnitude relationship determined by the magnitude determining unit 204 , a control unit 205 supplies a current to the windings of the three-phase motor 203 from the single-phase AC power supply 201 , and controls the conduction of each of the bidirectional switches 202 a to 202 f to allow circulation of a regenerative current from the windings of the three-phase motor 203 .

According to PTL 1, the matrix converter 200 having the above configuration allows the motor driving current to be stable, highly efficient, and highly reliable without a short circuit.

PTL 2 discloses a similar technique for driving a three-phase motor with a single-phase AC power supply, using a matrix converter.

Patent Literature

[PTL 1] Japanese Unexamined Patent Application Publication No. 2011-4449

[PTL 2] Japanese Unexamined Patent Application Publication No. 2010-154714

Technical Problem

However, with conventional matrix converters that convert a single-phase AC voltage into a three-phase AC voltage, the voltage of each phase of the motor is half the single-phase AC voltage. Consequently, the output of the motor decreases, and thus it is necessary to add, for example, a booster circuit between the single-phase AC power supply and the matrix converter. This causes such problems as: a shortened lifespan of the product due to an electrolytic capacitor of the booster circuit; power loss in the booster circuit; and an increased size resulting from the addition of the booster circuit.

It is an object of the present invention to provide: a power conversion apparatus and a power conversion method for converting a single-phase AC voltage into a three-phase AC voltage to make the voltage of each phase of the motor equal to the single-phase AC voltage; a motor system which includes such a power conversion apparatus; and a three-phase motor suitable for being driven by such a power conversion apparatus.

Solution to Problem

In order to solve the above-described problems, a power conversion apparatus according to an aspect of the present invention is a power conversion apparatus which converts an input voltage which is a single-phase AC voltage into output voltages forming a three-phase AC voltage, the power conversion apparatus including: a pair of input terminals to which the input voltage is applied; a pair of first output terminals which output a first one of the output voltages as a first-phase output voltage; a pair of second output terminals which output a second one of the output voltages as a second-phase output voltage; a pair of third output terminals which output a third one of the output voltages as a third-phase output voltage; four first bidirectional switches each corresponding to a different combination of one of the paired input terminals and one of the paired first output terminals to switch connection and disconnection between the corresponding input terminal and first output terminal according to a corresponding one of first control signals; four second bidirectional switches each corresponding to a different combination of one of the paired input terminals and one of the paired second output terminals to switch connection and disconnection between the corresponding input terminal and second output terminal according to a corresponding one of second control signals; four third bidirectional switches each corresponding to a different combination of one of the paired input terminals and one of the paired third output terminals to switch connection and disconnection between the corresponding input terminal and third output terminal according to a corresponding one of third control signals; a target voltage designating unit configured to designate (i) a first target voltage representing, using a first one of AC voltages forming a three-phase AC voltage, consecutive target values of the first-phase output voltage, (ii) a second target voltage representing, using a second one of the AC voltages forming the three-phase AC voltage, consecutive target values of the second-phase output voltage, and (iii) a third target voltage representing, using a third one of the AC voltages forming the three-phase AC voltage, consecutive target values of the third-phase output voltage; a control signal generating unit configured to (i) generate the first control signals to cyclically connect and disconnect the pair of the input terminals and the pair of the first output terminals via the first bidirectional switches at a duty cycle corresponding to a ratio of an instantaneous absolute value of the first target voltage to an instantaneous absolute value of the input voltage during a time period in which the instantaneous absolute value of the input voltage is greater than the instantaneous absolute value of the first target voltage, (ii) generate the second control signals to cyclically connect and disconnect the pair of the input terminals and the pair of the second output terminals via the second bidirectional switches at a duty cycle corresponding to a ratio of an instantaneous absolute value of the second target voltage to the instantaneous absolute value of the input voltage during a time period in which the instantaneous absolute value of the input voltage is greater than the instantaneous absolute value of the second target voltage, and (iii) generate the third control signals to cyclically connect and disconnect the pair of the input terminals and the pair of the third output terminals via the third bidirectional switches at a duty cycle corresponding to a ratio of an instantaneous absolute value of the third target voltage to the instantaneous absolute value of the input voltage during a time period in which the instantaneous absolute value of the input voltage is greater than the instantaneous absolute value of the third target voltage; and a driver which supplies the generated first control signals to the first bidirectional switches, the generated second control signals to the second bidirectional switches, and the generated third control signals to the third bidirectional switches.

Advantageous Effects of Invention

The power conversion apparatus having the above configuration can convert a single-phase AC voltage into a three-phase AC voltage by the switching operation of the bidirectional switches. As a result, the three-phase AC voltage can be generated from the single-phase AC voltage with high efficiency without using a capacitor having a possibility of undermining the long-term reliability of the apparatus and without reducing the output of the motor.

A three-phase AC voltage generated from commercial power supply for households using the power conversion apparatus may be supplied independently to the winding of each phase of a three-phase induction motor or the winding of each phase of a three-phase synchronous motor. By doing so, it is possible to provide a broad range of home appliances with a highly reliable and long-life motor system which does not include a capacitor.

FIG. 1A is a block diagram illustrating an example of a functional configuration of a motor system including a power conversion apparatus according to Embodiment 1.

FIG. 1B is a block diagram illustrating another example of a motor system according to Embodiment 1.

FIG. 2 is a block diagram illustrating an example of a detailed configuration of a matrix switch and a three-phase motor according to Embodiment 1.

FIG. 3A is a graph illustrating an example of waveforms of main voltages used in a power conversion method according to Embodiment 1.

FIG. 3B is a graph illustrating an example of waveforms of main voltages used in a power conversion method according to Embodiment 1.

FIG. 3C is a graph illustrating an example of waveforms of main voltages used in a power conversion method according to Embodiment 1.

FIG. 3D illustrates apparent power of a single-phase AC power supply when a motor is actuated according to Embodiment 1.

FIG. 3E illustrates apparent power of a single-phase AC power supply when a motor is actuated according to Embodiment 1.

FIG. 3F illustrates apparent power of a single-phase AC power supply when a motor is actuated according to Embodiment 1.

FIG. 3G illustrates apparent power of a single-phase AC power supply when a motor is actuated according to Embodiment 1.

FIG. 4 is a timing chart illustrating an example of gate signals according to Embodiment 1.

FIG. 5A is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 1.

FIG. 5B is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 1.

FIG. 5C is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 1.

FIG. 5D is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 1.

FIG. 5E is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 1.

FIG. 5F is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 1.

FIG. 5G is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 1.

FIG. 5H is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 1.

FIG. 6A is a graph illustrating an example of output voltages obtained by a single-phase to three-phase conversion performed by a typical matrix converter.

FIG. 6B is a graph illustrating an example of output voltages obtained by a single-phase to three-phase conversion performed by a power conversion apparatus according to Embodiment 1.

FIG. 7 is a functional block diagram illustrating another example of a motor system according to Embodiment 1.

FIG. 8 is a functional block diagram illustrating another example of a motor system according to Embodiment 1.

FIG. 9 is a timing chart illustrating another example of gate signals according to Embodiment 1.

FIG. 10 is a timing chart illustrating an example of gate signals according to Variation 1 of Embodiment 1.

FIG. 11A is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 1 of Embodiment 1.

FIG. 11B is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 1 of Embodiment 1.

FIG. 11C is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 1 of Embodiment 1.

FIG. 11D is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 1 of Embodiment 1.

FIG. 11E is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 1 of Embodiment 1.

FIG. 11F is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 1 of Embodiment 1.

FIG. 11G is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 1 of Embodiment 1.

FIG. 11H is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 1 of Embodiment 1.

FIG. 12 is a timing chart illustrating an example of gate signals according to Variation 2 of Embodiment 1.

FIG. 13A is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 2 of Embodiment 1.

FIG. 13B is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 2 of Embodiment 1.

FIG. 13C is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 2 of Embodiment 1.

FIG. 13D is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 2 of Embodiment 1.

FIG. 13E is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 2 of Embodiment 1.

FIG. 13F is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 2 of Embodiment 1.

FIG. 13G is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 2 of Embodiment 1.

FIG. 13H is a circuit diagram illustrating an example of the states of switches and a current path according to Variation 2 of Embodiment 1.

FIG. 14 is a timing chart illustrating an example of gate signals according to Embodiment 2.

FIG. 15 is a timing chart illustrating another example of gate signals according to Embodiment 2.

FIG. 16 is a timing chart illustrating another example of gate signals according to Embodiment 2.

FIG. 17A is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 2.

FIG. 17B is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 2.

FIG. 17C is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 2.

FIG. 17D is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 2.

FIG. 18 is a timing chart illustrating another example of gate signals according to Embodiment 2.

FIG. 19A is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 2.

FIG. 19B is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 2.

FIG. 19C is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 2.

FIG. 19D is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 2.

FIG. 19E is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 2.

FIG. 19F is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 2.

FIG. 19G is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 2.

FIG. 19H is a circuit diagram illustrating an example of the states of switches and a current path according to Embodiment 2.

FIG. 20 is a circuit diagram of a conventional matrix converter.

A power conversion apparatus according to an aspect of the present invention is a power conversion apparatus which converts an input voltage which is a single-phase AC voltage into output voltages forming a three-phase AC voltage, the power conversion apparatus including: a pair of input terminals to which the input voltage is applied; a pair of first output terminals which output a first one of the output voltages as a first-phase output voltage; a pair of second output terminals which output a second one of the output voltages as a second-phase output voltage; a pair of third output terminals which output a third one of the output voltages as a third-phase output voltage; four first bidirectional switches each corresponding to a different combination of one of the paired input terminals and one of the paired first output terminals to switch connection and disconnection between the corresponding input terminal and first output terminal according to a corresponding one of first control signals; four second bidirectional switches each corresponding to a different combination of one of the paired input terminals and one of the paired second output terminals to switch connection and disconnection between the corresponding input terminal and second output terminal according to a corresponding one of second control signals; four third bidirectional switches each corresponding to a different combination of one of the paired input terminals and one of the paired third output terminals to switch connection and disconnection between the corresponding input terminal and third output terminal according to a corresponding one of third control signals; a target voltage designating unit configured to designate (i) a first target voltage representing, using a first one of AC voltages forming a three-phase AC voltage, consecutive target values of the first-phase output voltage, (ii) a second target voltage representing, using a second one of the AC voltages forming the three-phase AC voltage, consecutive target values of the second-phase output voltage, and (iii) a third target voltage representing, using a third one of the AC voltages forming the three-phase AC voltage, consecutive target values of the third-phase output voltage; a control signal generating unit configured to (i) generate the first control signals to cyclically connect and disconnect the pair of the input terminals and the pair of the first output terminals via the first bidirectional switches at a duty cycle corresponding to a ratio of an instantaneous absolute value of the first target voltage to an instantaneous absolute value of the input voltage during a time period in which the instantaneous absolute value of the input voltage is greater than the instantaneous absolute value of the first target voltage, (ii) generate the second control signals to cyclically connect and disconnect the pair of the input terminals and the pair of the second output terminals via the second bidirectional switches at a duty cycle corresponding to a ratio of an instantaneous absolute value of the second target voltage to the instantaneous absolute value of the input voltage during a time period in which the instantaneous absolute value of the input voltage is greater than the instantaneous absolute value of the second target voltage, and (iii) generate the third control signals to cyclically connect and disconnect the pair of the input terminals and the pair of the third output terminals via the third bidirectional switches at a duty cycle corresponding to a ratio of an instantaneous absolute value of the third target voltage to the instantaneous absolute value of the input voltage during a time period in which the instantaneous absolute value of the input voltage is greater than the instantaneous absolute value of the third target voltage; and a driver which supplies the generated first control signals to the first bidirectional switches, the generated second control signals to the second bidirectional switches, and the generated third control signals to the third bidirectional switches.

With such a configuration, the single-phase AC voltage can be converted into the three-phase AC voltage through the switching control by the bidirectional switches. As a result, the three-phase AC voltage can be generated from the single-phase AC voltage with high efficiency without using a booster circuit which includes a capacitor having a possibility of undermining the long-term reliability of the apparatus.

The target voltage designating unit may be configured to designate the first target voltage, the second target voltage, and the third target voltage using AC voltages forming a three-phase AC voltage which have: an amplitude 1/√3 times smaller than an amplitude of the input voltage; a frequency identical to a frequency of the input voltage; and phase differences relative to the input voltage.

With such a configuration, a total duty cycle of 100% can be obtained from the output voltages of the three phases, and thus the input voltage can be effectively and stably converted into the output voltage of each phase.

The control signal generating unit may be configured to (i) generate the first control signals to (a) make a straight connection between the pair of the input terminals and the pair of the first output terminals during a time period in which the input voltage and the first target voltage have a same polarity and (b) make a cross connection between the pair of the input terminals and the pair of the first output terminals during a time period in which the input voltage and the first target voltage have different polarities, (ii) generate the second control signals to (a) make a straight connection between the pair of the input terminals and the pair of the second output terminals during a time period in which the input voltage and the second target voltage have a same polarity and (b) make a cross connection between the pair of the input terminals and the pair of the second output terminals during a time period in which the input voltage and the second target voltage have different polarities, and (iii) generate the third control signals to (a) make a straight connection between the pair of the input terminals and the pair of the third output terminals during a time period in which the input voltage and the third target voltage have a same polarity and (b) make a cross connection between the pair of the input terminals and the pair of the third output terminals during a time period in which the input voltage and the third target voltage have different polarities.

With such a configuration, it is possible to obtain a large output voltage having an amplitude twice larger than the amplitude of the input voltage at maximum.

The control signal generating unit may be configured to (i) generate the first control signals to constantly connect the pair of the input terminals and the pair of the first output terminals during a time period in which the instantaneous absolute value of the input voltage is less than or equal to the instantaneous absolute value of the first target voltage, (ii) generate the second control signals to constantly connect the pair of the input terminals and the pair of the second output terminals during a time period in which the instantaneous absolute value of the input voltage is less than or equal to the instantaneous absolute value of the second target voltage, and (iii) generate the second control signals to constantly connect the pair of the input terminals and the pair of the third output terminals during a time period in which the instantaneous absolute value of the input voltage is less than or equal to the instantaneous absolute value of the third target voltage.

With such a configuration, the effective use of the input voltage is possible because the first-phase output voltage, the second-phase output voltage, or the three-phase output voltage is regulated to have the largest generable value when the input voltage is insufficient relative to the first target voltage, the second target voltage, or the third target voltage.

The control signal generating unit may be configured to (i) generate the first control signals to constantly disconnect the pair of the input terminals and the pair of the first output terminals during a time period in which the instantaneous absolute value of the input voltage is less than or equal to the instantaneous absolute value of the first target voltage, (ii) generate the second control signals to constantly disconnect the pair of the input terminals and the pair of the second output terminals during a time period in which the instantaneous absolute value of the input voltage is less than or equal to the instantaneous absolute value of the second target voltage, and (iii) generate the third control signals to constantly disconnect the pair of the input terminals and the pair of the third output terminals during a time period in which the instantaneous absolute value of the input voltage is less than or equal to the instantaneous absolute value of the third target voltage.

With such a configuration, fluctuations of the input voltage can be reduced because the voltage supply is cut off when the input voltage is insufficient relative to the first target voltage, the second target voltage, or the third target voltage. In addition, the combination of switches which form a part of the path of a circulating current can be changed while the voltage supply is cut off, and thus there is no need to accurately change the switches when the input voltage becomes 0 V. As a result, misoperation can be prevented.

The control signal generating unit may be configured to (i) generate the first control signals to short-circuit the pair of the first output terminals when the pair of the input terminals and the pair of the first output terminals are disconnected, (ii) generate the second control signals to short-circuit the pair of the second output terminals when the pair of the input terminals and the pair of the second output terminals are disconnected, and (iii) generate the third control signals to short-circuit the pair of the third output terminals when the pair of the input terminals and the pair of the third output terminals are disconnected.

With such a configuration, the power efficiency increases because it is possible to allow the regenerative current from the load to circulate within the power conversion apparatus.

Each of the first bidirectional switches, each of the second bidirectional switches, and each of the third bidirectional switches may include two unidirectional switches connected in inverse parallel, each of the unidirectional switches may change between a forward-directional conducting state and a non-conducting state according to either a corresponding one of the first control signals, a corresponding one of the second control signals, or a corresponding one of the third control signals and not conduct in an opposite direction, and the control signal generating unit may be configured to (i) generate, for short-circuiting the pair of the first output terminals, the first control signals to place, in the conducting state, all the unidirectional switches included in plural ones of the first bidirectional switches which are used for short-circuiting the pair of the first output terminals, (ii) generate, for short-circuiting the pair of the second output terminals, the second control signals to place, in the conducting state, all the unidirectional switches included in plural ones of the second bidirectional switches which are used for short-circuiting the pair of the second output terminals, and (iii) generate, for short-circuiting the pair of the third output terminals, the third control signals to place, in the conducting state, all the unidirectional switches included in plural ones of the third bidirectional switches which are used for short-circuiting the pair of the third output terminals.

With such a configuration, it is possible to allow the regenerative current from the load to circulate within the power conversion apparatus irrespective of the direction of the regenerative current.

Each of the first bidirectional switches, each of the second bidirectional switches, and each of the third bidirectional switches may include two unidirectional switches connected in inverse parallel, each of the unidirectional switches may change between a forward-directional conducting state and a non-conducting state according to either a corresponding one of the first control signals, a corresponding one of the second control signals, or a corresponding one of the third control signals and not conduct in an opposite direction, and the control signal generating unit may be configured to generate the first control signals, the second control signals, and the third control signals to (i) change between the conducting state and the non-conducting state of one of the two unidirectional switches to which the input voltage is applied in a forward direction and (ii) constantly place, in the conducting state, the other of the two unidirectional switches to which the input voltage is applied in the opposite direction.

With such a configuration, the power consumption required for the switching operations can be decreased by reducing the number of switching operations performed for changing the states of the unidirectional switches.

The control signal generating unit may be configured to (i) generate the first control signals to place, in a conducting state, plural ones of the first bidirectional switches which are determined depending on a polarity of the input voltage, when the pair of the input terminals and the pair of the first output terminals are connected, (ii) generate the second control signals to place, in a conducting state, plural ones of the second bidirectional switches which are determined depending on the polarity of the input voltage, when the pair of the input terminals and the pair of the second output terminals are connected, and (iii) generate the third control signals to place, in a conducting state, plural ones of the third bidirectional switches which are determined depending on the polarity of the input voltage, when the pair of the input terminals and the pair of the third output terminals are connected.

With such a configuration, the heat generated by each bidirectional switch is leveled out by leveling out the number of switching operations among the bidirectional switches. Thus, it is possible to reduce the disadvantages of decreased power and lower reliability caused by local overheating.

The control signal generating unit may be configured to generate the first control signals, the second control signals, and the third control signals to avoid overlap of a time period in which the pair of the input terminals and the pair of the first output terminals are connected, a time period in which the pair of the input terminals and the pair of the second output terminals are connected, and a time period in which the pair of the input terminals and the pair of the third output terminals are connected.

With such a configuration, the power feeding of the three phases can be performed in time periods which do not overlap each other in each cycle, as long as the total duty cycle for the three phases does not exceed 100%.

A power conversion method according to an aspect of the present invention is a power conversion method for converting an input voltage which is a single-phase AC voltage into output voltages forming a three-phase AC voltage, the power conversion method including: receiving the input voltage at a pair of input terminals; designating (i) a first target voltage representing, using a first one of AC voltages forming a three-phase AC voltage, consecutive target values of a first-phase output voltage that is a first one of the output voltages, (ii) a second target voltage representing, using a second one of the AC voltages forming the three-phase AC voltage, consecutive target values of a second-phase output voltage that is a second one of the output voltages, and (iii) a third target voltage representing, using a third one of the AC voltages forming the three-phase AC voltage, consecutive target values of a third-phase output voltage that is a third one of the output voltages; cyclically connecting and disconnecting the pair of the input terminals and a pair of first output terminals via first bidirectional switches at a duty cycle corresponding to a ratio of an instantaneous absolute value of the first target voltage to an instantaneous absolute value of the input voltage during a time period in which the instantaneous absolute value of the input voltage is greater than the instantaneous absolute value of the first target voltage; cyclically connecting and disconnecting the pair of the input terminals and a pair of second output terminals via second bidirectional switches at a duty cycle corresponding to a ratio of an instantaneous absolute value of the second target voltage to the instantaneous absolute value of the input voltage during a time period in which the instantaneous absolute value of the input voltage is greater than the instantaneous absolute value of the second target voltage; and cyclically connecting and disconnecting the pair of the input terminals and a pair of third output terminals via third bidirectional switches at a duty cycle corresponding to a ratio of an instantaneous absolute value of the third target voltage to the instantaneous absolute value of the input voltage during a time period in which the instantaneous absolute value of the input voltage is greater than the instantaneous absolute value of the third target voltage.

With such a configuration, it is possible to obtain a highly efficient and reliable power conversion method for converting a single-phase AC voltage into a three-phase AC voltage.

A motor system according to an aspect of the present invention is a motor system including: the above-described power conversion apparatus; a three-phase motor including: a first axis winding; a second axis winding; a third axis winding; a rotor; a pair of first power receiving terminals connected to the first axis winding; a pair of second power receiving terminals connected to the second axis winding; and a pair of third power receiving terminals connected to the third axis winding, the first axis winding, the second axis winding, and the third axis winding being not electrically connected within the three-phase motor; first feed lines connecting the pair of the first output terminals of the power conversion apparatus and the pair of the first power receiving terminals of the three-phase motor; and second feed lines connecting the pair of the second output terminals of the power conversion apparatus and the pair of the second power receiving terminals of the three-phase motor; and third feed lines connecting the pair of the third output terminals of the power conversion apparatus and the pair of the third power receiving terminals of the three-phase motor.

With such a configuration, a long-life three-phase motor which does not include a capacitor can be driven using the three-phase AC voltage converted from the single-phase AC voltage by the power conversion apparatus.

In the motor system, the three-phase motor may include a rotation angle sensor which outputs a rotation angle signal indicating consecutive rotation amounts of the rotor, the power conversion apparatus may further include a rotation angle obtaining unit configured to obtain the rotation angle signal, and the target voltage designating unit may be configured to perform vector control to change at least one of amplitude, frequency, and phase of the first target voltage, the second target voltage, and the third target voltage based on a difference between a rotation speed of the rotor determined from the obtained rotation angle signal and a speed command value.

In the motor system, the power conversion apparatus may further include: a current sensor which outputs current amount signals each indicating consecutive current amounts flowing in either the pair of the first output terminals, the pair of the second output terminals, or the pair of the third output terminals; and a current amount obtaining unit configured to obtain the current amount signals, and the target voltage designating unit may be configured to perform speed sensorless vector control to estimate a rotation speed of the rotor using the obtained consecutive current amounts, and change at least one of amplitude, frequency, and phase of the first target voltage, the second target voltage, and the third target voltage based on a difference between the estimated rotation speed and a speed command value.

With such a configuration, a motor system having a high controllability can be obtained.

A three-phase motor according to an aspect of the present invention is a three-phase motor including: a first axis winding; a second axis winding; a third axis winding; a rotor; a pair of first power receiving terminals connected to the first axis winding; a pair of second power receiving terminals connected to the second axis winding; and a pair of third power receiving terminals connected to the third axis winding, wherein the first axis winding, the second axis winding, and the third axis winding are not electrically connected within the three-phase motor.

With such a configuration, it is possible to obtain a long-life three-phase motor which does not include a capacitor and is suitable for being driven by the power conversion apparatus described above.

Hereinafter, a power conversion apparatus, a power conversion method, a motor system which includes such a power conversion apparatus, and a three-phase motor suitable for being driven by such a power conversion apparatus according to an aspect of the present invention will be described with reference to the accompanying drawings.

Each of the embodiments described below illustrates a specific example of the present invention. The numerical values, shapes, materials, structural elements, the arrangement and connection of the structural elements etc., shown in the following embodiments are mere examples, and are therefore not intended to limit the present invention. Among the structural elements in the following embodiments, structural elements not recited in any one of the independent claims are described as arbitrary structural elements.

FIG. 1A is a block diagram illustrating an example of a functional configuration of a motor system including a power conversion apparatus according to Embodiment 1. The motor system illustrated in FIG. 1A includes a power conversion apparatus 1 , a three-phase motor 5 , and feed lines connecting the power conversion apparatus 1 and the three-phase motor 5 .

A single-phase AC power supply 2 supplies a single-phase AC voltage to the motor system. The single-phase AC power supply 2 may be a commercial power supply for households, for example.

The power conversion apparatus 1 converts an input voltage which is a single-phase AC voltage into output voltages forming a three-phase AC voltage. The power conversion apparatus 1 includes: a pair of input terminals 3 and 4 to which the single-phase AC power supply 2 applies the input voltage; a pair of first output terminals 6 and 7 which output a first one of the output voltages as a first-phase output voltage; a pair of second output terminals 8 and 9 which output a second one of the output voltages as a second-phase output voltage; a pair of third output terminals 10 and 33 which output a third one of the output voltages as a third-phase output voltage; a matrix switch 32 ; and a switch controller 26 .

FIG. 2 is a block diagram illustrating an example of a detailed configuration of the three-phase motor 5 and the matrix switch 32 .

The three-phase motor 5 is a three-phase induction motor or a three-phase synchronous motor, for example, and includes a first axis winding 51 , a second axis winding 52 , a third axis winding 53 , a rotor 54 , a pair of first power receiving terminals 56 and 57 connected to the first axis winding 51 , a pair of second power receiving terminals 58 and 59 connected to the second axis winding 52 , and a pair of third power receiving terminals 60 and 61 connected to the third axis winding 53 .

The first axis winding 51 , the second axis winding 52 , and the third axis winding 53 are not electrically connected within the three-phase motor 5 . The first axis winding 51 , the second axis winding 52 , and the third axis winding 53 may have the same electrical characteristics. The first power receiving terminals 56 and 57 are connected to the first output terminals 6 and 7 of the power conversion apparatus 1 via first feed lines, the second power receiving terminals 58 and 59 are connected to the second output terminals 8 and 9 of the power conversion apparatus 1 via second feed lines, and the third power receiving terminals 60 and 61 are connected to the third output terminals 10 and 33 of the power conversion apparatus 1 via third feed lines. It is to be noted that the number of the first axis winding 51 , the second axis winding 52 , and the third axis winding 53 need not be one each. It is also possible to form a multipolar motor using two or more first axis windings 51 , second axis windings 52 , and third axis windings 53 , given that the number is the same for the first, second, and third axis windings 51 , 52 , and 53 .

The matrix switch 32 includes first bidirectional switches 11 to 14 , second bidirectional switches 15 to 18 , and third bidirectional switches 19 to 22 .

The first bidirectional switches 11 to 14 each correspond to a different combination of the input terminal 3 or 4 and the first output terminal 6 or 7 , and switch between connection and disconnection between the corresponding one of the input terminals 3 and 4 and the corresponding one of the first output terminals 6 and 7 according to a corresponding one of first control signals G 1 a to G 4 b supplied by the switch controller 26 .

The second bidirectional switches 15 to 18 each correspond to a different combination of the input terminal 3 or 4 and the second output terminal 8 or 9 , and switch between connection and disconnection between the corresponding one of the input terminals 3 and 4 and the corresponding one of the second output terminals 8 and 9 according to a corresponding one of second control signals G 5 a to G 8 b supplied by the switch controller 26 .

The third bidirectional switches 19 to 22 each correspond to a different combination of the input terminal 3 or 4 and the third output terminal 10 or 33 , and switch between connection and disconnection between the corresponding one of the input terminals 3 and 4 and the corresponding one of the third output terminals 10 and 33 according to a corresponding one of third control signals G 9 a to G 12 b supplied by the switch controller 26 .

As illustrated with the representative first bidirectional switch 13 , each of the first bidirectional switches 11 to 14 , each of the second bidirectional switches 15 to 18 , and each of the third bidirectional switches 19 to 22 may include, for example, two unidirectional switches connected in inverse parallel.

For example, a single unidirectional switch may be a reverse-blocking Isolated Gate Bipolar Transistor (IGBT) M 1 or M 2 , or may be formed as a circuit in which an IGBT M 3 and a diode D 1 are connected in series or a circuit in which an IGBT M 4 and a diode D 2 are connected in series.

Each unidirectional switch changes its state between a unidirectional conducting state and a non-conducting state according to one of the first control signals G 1 a to G 4 b , the second control signals G 5 a to G 8 b , and the third control signals G 9 a to G 12 b , and does not conduct in the opposite direction.

Each bidirectional switch can be formed with a single element by using a bidirectional, gallium nitride (GaN)-based Hetero Field Effect Transistor (HFET) M 5 . In the case of using the bidirectional, GaN-based HFET, a bidirectional switch can be formed by providing, between the source and drain, two gates to which control signals independent of each other can be applied.

Forming each bidirectional switch with a single element reduces the circuit area. Additionally, the two gates being adjacent to each other in the element allow the two gate signal lines to be formed with substantially the same length, thereby reducing delay between the gate signals. As a result, the control over the dead time and the commutation circuit increases, and thus misoperation can be prevented.

The state of each bidirectional switch described above can be changed to any of the following states: a conducting state in which a current flows bidirectionally; a conducting state in which a current flows only in the upward direction or the downward direction of the drawing; and a non-conducting state.

The matrix switch 32 can connect, by straight connection or cross connection, and disconnect the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 via the first bidirectional switches 11 to 14 according to the first control signals G 1 a to G 4 b.

Here, the straight connection between the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 is defined as connection between the input terminals 3 and 4 and the first output terminals 6 and 7 in such combinations that the input voltage applied to the input terminals 3 and 4 is supplied to the first output terminals 6 and 7 with the same polarity (also referred to as non-inverting voltage supply).

The cross connection between the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 is defined as connection between the input terminals 3 and 4 and the first output terminals 6 and 7 in such combinations that the input voltage applied to the input terminals 3 and 4 is supplied to the first output terminals 6 and 7 with the opposite polarity (also referred to as inverting voltage supply).

The disconnection between the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 is defined as disconnection of at least one of the input terminals 3 and 4 from both of the first output terminals 6 and 7 to cut off the supply of the input voltage applied to the pair of the input terminals 3 and 4 , to the pair of the first output terminals 6 and 7 .

Similarly, the matrix switch 32 can connect, by straight connection or cross connection, and disconnect the pair of the input terminals 3 and 4 and the pair of the second output terminals 8 and 9 via the second bidirectional switches 15 to 18 according to the second control signals G 5 a to G 8 b . The definitions of the straight connection, cross connection, and disconnection between the pair of the input terminals 3 and 4 and the pair of the second output terminals 8 and 9 are the same as those described above.

Similarly, the matrix switch 32 can connect, by straight connection or cross connection, and disconnect the pair of the input terminals 3 and 4 and the pair of the third output terminals 10 and 33 via the third bidirectional switches 19 to 22 according to the third control signals G 9 a to G 12 b . The definitions of the straight connection, cross connection, and disconnection between the pair of the input terminals 3 and 4 and the pair of the third output terminals 10 and 33 are the same as those described above.

The switch controller 26 is a controller of the matrix switch 32 . The switch controller 26 generates the first control signals G 1 a to G 4 b , the second control signals G 5 a to G 8 b , and the third control signals G 9 a to G 12 b , and supplies them to the matrix switch 32 so that the input voltage that is a single-phase AC voltage is converted into the output voltages forming a three-phase AC voltage via the matrix switch 32 .

The switch controller 26 may be implemented as an analog circuit including an oscillator, a comparator, a multiplier, and so on. The switch controller 26 may also be implemented as a software function performed by a processor executing a certain program.

As illustrated in FIG. 1A , the switch controller 26 includes a target voltage designating unit 23 , a control signal generating unit 24 , and a driver 25 .

The target voltage designating unit 23 designates (i) a first target voltage representing, using a first one of AC voltages forming a three-phase AC voltage, consecutive target values of the first-phase output voltage, (ii) a second target voltage representing, using a second one of the AC voltages forming the three-phase AC voltage, consecutive target values of the second-phase output voltage, and (iii) a third target voltage representing, using a third one of AC voltages forming the three-phase AC voltage, consecutive target values of the third-phase output voltage.

The control signal generating unit 24 generates the first control signals G 1 a to G 4 b , the second control signals G 5 a to G 8 b , and the third control signals G 9 a to G 12 b.

The first control signals G 1 a to G 4 b are control signals for cyclically connecting and disconnecting the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 . The first control signals G 1 a to G 4 b are generated based on a comparison between the input voltage and the first target voltage in terms of the polarity and the instantaneous absolute value.

The second control signals G 5 a to G 8 b are control signals for cyclically connecting and disconnecting the pair of the input terminals 3 and 4 and the pair of the second output terminals 8 and 9 . The second control signals G 5 a to G 8 b are generated based on a comparison between the input voltage and the second target voltage in terms of the polarity and the instantaneous absolute value.

The third control signals G 9 a to G 12 b are control signals for cyclically connecting and disconnecting the pair of the input terminals 3 and 4 and the pair of the third output terminals 10 and 33 . The third control signals G 9 a to G 12 b are generated based on a comparison between the input voltage and the third target voltage in terms of the polarity and the instantaneous absolute value.

When the input terminal 4 is grounded with sufficiently low impedance, the control signal generating unit 24 obtains the voltage at the input terminal 3 to detect, as the input voltage, the voltage at the input terminal 3 relative to the ground voltage.

Irrespective of whether the input terminal 4 is grounded or not, the control signal generating unit 24 may detect the voltage between the input terminals 3 and 4 to detect this voltage between the terminals as the input voltage, as illustrated in FIG. 1B .

The driver 25 supplies the generated first control signals G 1 a to G 4 b to the first bidirectional switches 11 to 14 , the generated second control signals G 5 a to G 8 b to the second bidirectional switches 15 to 18 , and the generated third control signals G 9 a to G 12 b to the third bidirectional switches 19 to 22 .

The following describes a power conversion method performed by the power conversion apparatus 1 having the above configuration.

Each of FIG. 3A to FIG. 3C is a graph illustrating an example of waveforms of main voltages used in the power conversion method. Referring to FIG. 3A to FIG. 3C , the fundamental idea of the power conversion method will be first described.

Each of FIG. 3A to FIG. 3C illustrates a typical example of waveforms of input voltages in and −in, a first target voltage ref 1 , a second target voltage ref 2 , a third target voltage ref 3 , a first-phase output voltage out 1 , a second-phase output voltage out 2 , and a third-phase output voltage out 3 .

Any one of the input voltages in and −in is a single-phase AC voltage applied to the input terminals 3 and 4 from the single-phase AC power supply 2 . The input voltage in is a voltage at the input terminal 3 relative to the input terminal 4 , and the input voltage −in is a voltage at the input terminal 4 relative to the input terminal 3 .

As an example, the input voltage in is expressed as (√2) V sin (ωt) when a sinusoidal AC voltage having V as the effective value of the voltage is applied between the input terminals 3 and 4 . Here, ω denotes angular frequency, and ω is 2πf when the frequency of the sinusoidal AC voltage is f. In addition, t denotes time. When using the Japanese commercial power supply for households as the input voltage, V is 100 [V] and f is 50 [Hz] or 60 [Hz].

Each of the first target voltage ref 1 , the second target voltage ref 2 , and the third target voltage ref 3 is one of three AC voltages forming a three-phase AC voltage designated by the target voltage designating unit 23 . The first target voltage ref 1 , the second target voltage ref 2 , and the third target voltage ref 3 represent consecutive target values (that is, target values at respective points of time) of the first-phase output voltage out 1 , the second-phase output voltage out 2 , and the third-phase output voltage out 3 , respectively.

For example, when driving the three-phase motor using the first-phase output voltage out 1 , the second-phase output voltage out 2 , and the third-phase output voltage out 3 , AC voltages which are the same in frequency and different in phase are used as the first target voltage ref 1 , the second target voltage ref 2 , and the third target voltage ref 3 . The frequency, amplitude, and phase difference of the first target voltage ref 1 , the second target voltage ref 2 , and the third target voltage ref 3 are appropriately determined for controlling the rotation speed and/or torque and according to the structure of the three-phase motor being driven.

As an example, the first target voltage ref 1 , the second target voltage ref 2 , and the third target voltage ref 3 may be sinusoidal AC voltages having the same frequency as the frequency of the input voltage in, an amplitude 1/√3 times smaller than the amplitude of the input voltage in, and phase differences of −45 degrees, +75 degrees, and −165 degrees relative to the input voltage in. In this case, the first target voltage ref 1 is expressed as √(⅔) V sin (ωt−π/4), the second target voltage ref 2 is expressed as √(⅔) V sin (ωt+5π/12), and the third target voltage ref 3 is expressed as √(⅔) V sin (ωt−11π/12).

It is to be noted that the first target voltage ref 1 , the second target voltage ref 2 , and the third target voltage ref 3 may be given a phase difference of any value relative to the input voltage in as long as ref 2 has a phase difference of +120 degrees relative to ref 1 and ref 3 has a phase difference of −120 degrees relative to ref 1 . Given that ref 1 has a phase difference of φ relative to the input voltage in, the first target voltage ref 1 , the second target voltage ref 2 , and the third target voltage ref 3 are expressed as √(⅔) V sin (ωt+φ), √(⅔) V sin (ωt+2π/3+φ), and √(⅔) V sin (ωt−2π/3+φ), respectively.

Each of FIG. 3D to FIG. 3G is a plot of apparent power VA of the single-phase AC power supply 2 when a motor is actuated, for different values of φ. As is clear from FIG. 3D to FIG. 3G , the apparent power when the motor is actuated is lowest in the case of φ=π/4, which means that grid power demanded by the general households is lowest. In this case, the first target voltage ref 1 , the second target voltage ref 2 , and the third target voltage ref 3 have phase differences of +45 degrees, +165 degrees, and −75 degrees relative to the input voltage in, respectively.

The power conversion apparatus 1 converts the input voltage in into the first-phase output voltage out 1 based on the relationship between the input voltage in and the first target voltage ref 1 in terms of the sign and the instantaneous absolute value.

As illustrated in FIG. 3A , during the time periods T 2 , T 3 , T 6 and T 7 in which the instantaneous absolute value of the input voltage in is greater than the instantaneous absolute value of the first target voltage ref 1 (in other words, the absolute value of the input voltage is excessive), the power conversion apparatus 1 cyclically connects and disconnects the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 via the first bidirectional switches 11 to 14 to regulate the average of the first-phase output voltage out 1 in a short period of time (e.g., average for each cycle) to be the instantaneous value of the first target voltage ref 1 .

Such control may be performed through PWM control, for example. As the cycles of the PWM control, cycles sufficiently short compared to the cycles of the input voltage in, the first target voltage ref 1 , and the second target voltage ref 2 are used (e.g., cycles of a PWM carrier signal having a frequency of 20 kHz).

The PWM control consecutively changes the connection period per cycle so that the duty cycle, i.e., a ratio of a connection period to the PWM cycle, equals a ratio of the instantaneous value of the first target voltage ref 1 to the instantaneous value of the input voltage in. As a result, the average of the first-phase output voltage out 1 per cycle is regulated to be the instantaneous value of the first target voltage ref 1 . The waveform of the first-phase output voltage out 1 in FIG. 3A shows the average of the first-phase output voltage out 1 per cycle.

It is to be noted that such regulation can be performed not only by the PWM control but also by other known control methods such as Pulse Density Modulation (PDM) control which consecutively changes the length of each cycle with the connection period being constant.

During the time periods T 1 , T 4 , T 5 and T 8 in which the instantaneous absolute value of the input voltage in is less than or equal to the instantaneous absolute value of the first target voltage ref 1 (in other words, the absolute value of the input voltage is insufficient), the power conversion apparatus 1 constantly connects the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 via the first bidirectional switches 11 to 14 to regulate the absolute value of the first-phase output voltage out 1 to be the largest generable value.

However, during the time periods in which the absolute value of the input voltage is insufficient, the power conversion apparatus 1 may continuously disconnect the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 to make the first-phase output voltage out 1 zero (i.e., the voltage supply may be suspended). Such an embodiment will be described in detail later.

When connecting the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 , the power conversion apparatus 1 makes a straight connection during the time periods (T 1 , T 2 , T 5 , and T 6 ) in which the input voltage in and the first target voltage ref 1 have the same polarity, and makes a cross connection during the time periods (T 3 , T 4 , T 7 , and T 8 ) in which the input voltage in and the first target voltage ref 1 have different polarities.

In such a manner, the power conversion apparatus 1 converts the input voltage in into the first-phase output voltage out 1 .

Furthermore, the power conversion apparatus 1 converts the input voltage in into the second-phase output voltage out 2 based on the relationship between the input voltage in and the second target voltage ref 2 in terms of the sign and the instantaneous absolute value.

As illustrated in FIG. 3B , the relationship between the input voltage in and the first target voltage ref 1 established in terms of the sign and the instantaneous absolute value in the time periods T 1 to T 8 illustrated in FIG. 3A is identically established between the input voltage in and the second target voltage ref 2 in the time periods T 1 to T 8 illustrated in FIG. 3B . The power conversion apparatus 1 applies the same idea as described above to the input voltage in and the second target voltage ref 2 to convert the input voltage in into the second-phase output voltage out 2 . As with the waveform of the first-phase output voltage out 1 , the waveform of the second-phase output voltage out 2 in FIG. 3B is represented by the average per cycle.

Furthermore, the power conversion apparatus 1 converts the input voltage in into the third-phase output voltage out 3 based on the relationship between the input voltage in and the third target voltage ref 3 in terms of the sign and the instantaneous absolute value.

As illustrated in FIG. 3C , the relationship between the input voltage in and the first target voltage ref 1 established in terms of the sign and the instantaneous absolute value in the time periods T 1 to T 8 illustrated in FIG. 3A is identically established between the input voltage in and the third target voltage ref 3 in the time periods T 1 to T 8 illustrated in FIG. 3C . The power conversion apparatus 1 applies the same idea as described above to the input voltage in and the third target voltage ref 3 to convert the input voltage in into the third-phase output voltage out 3 . As with the waveform of the first-phase output voltage out 1 , the waveform of the third-phase output voltage out 3 in FIG. 3C is represented by the average per cycle.

Next, the following describes the processing performed by the switch controller 26 to execute such a power conversion method.

FIG. 4 is a timing chart illustrating an example of the waveforms of the input voltages in and −in, the target voltage ref 1 designated by the target voltage designating unit 23 , the first control signals G 1 a to G 4 b generated by the control signal generating unit 24 , and the output voltage out 1 . The waveform of the output voltage out 1 is represented by the average of the output voltage out 1 per cycle. The time periods T 1 to T 8 correspond to the time periods T 1 to T 8 in FIG. 3A , respectively.

In FIG. 4 and the following description, the first bidirectional switches 11 to 14 are denoted as SW 11 to SW 14 , respectively, and the first control signals G 1 a to G 4 b are denoted as gate signals G 1 a to G 4 b of SW 11 to SW 14 , respectively. The ON level of the gate signals G 1 a to G 4 b indicates a signal level for placing the unidirectional switches forming the SW 11 to SW 14 in the conducting state, whereas the OFF level of the gate signals G 1 a to G 4 b indicates a signal level for placing the unidirectional switches forming the SW 11 to SW 14 in the non-conducting state.

FIG. 5A to FIG. 5H are circuit diagrams each illustrating: the conduction states of SW 11 to SW 14 that are set according to the gate signals G 1 a to G 4 b illustrated in FIG. 4 in the time periods T 1 to T 8 ; and the current path of the first axis winding 51 determined accordingly. In FIG. 5A to FIG. 5H , the conducting state and the non-conducting state of each of the unidirectional switches forming SW 11 to SW 14 are denoted by a solid line and a dotted line, respectively, and the current path of the first axis winding 51 is denoted by a thick dashed arrow.

For simplicity, FIG. 4 , FIG. 5A to FIG. 5H , and the following description focus on the first target voltage ref 1 , the gate signals G 1 a to G 4 b , and SW 11 to SW 14 which are for converting the input voltage in into the first-phase output voltage out 1 .

It is to be noted that the same holds true for: the second target voltage ref 2 , the second control signals G 5 a to G 8 b , and the bidirectional switches 15 to 18 which are for converting the input voltage in into the second-phase output voltage out 2 ; and the third target voltage ref 3 , the third control signals G 9 a to G 12 b , and the bidirectional switches 19 to 22 which are for converting the input voltage in into the third-phase output voltage out 3 .

The target voltage designating unit 23 designates the first target voltage ref 1 that is a voltage of one of the three phases of the three-phase AC voltage. For example, the target voltage designating unit 23 designates the first target voltage ref 1 by actually generating the first target voltage ref 1 using an oscillator or by showing the consecutive instantaneous values of the first target voltage ref 1 as time-series data.

The control signal generating unit 24 consecutively (e.g., per PWM cycle) determines one of the time periods T 1 to T 8 as the current period based on a comparison between the instantaneous value of the input voltage in and the instantaneous value of the first target voltage ref 1 . The control signal generating unit 24 then generates the gate signals G 1 a to G 4 b for performing one of the continuous non-inverting voltage supply, the non-inverting voltage supply through the PWM control, the continuous inverting voltage supply, and the inverting voltage supply through the PWM control, according to the determined time period.

In the time periods T 1 and T 5 , the gate signals G 1 a to G 4 b for the continuous non-inverting voltage supply are generated.

The control signal generating unit 24 determines the time period T 1 as the current period based on 0<in≦ref 1 (condition 1), and determines the time period T 5 as the current period based on 0>in≧ref 1 (condition 5).

Upon determination of the time period T 1 or T 5 , the control signal generating unit 24 sets the gate signals G 1 a and G 2 b of SW 12 and the gate signals G 3 a and G 3 b of SW 13 to the ON level, and sets the gate signals G 1 a and G 1 b of SW 11 and the gate signals G 4 a and G 4 b of SW 14 to the OFF level.

According to such gate signals G 1 a to G 4 b , in the time periods T 1 and T 5 , the conduction states of SW 11 to SW 14 and the current path of the first axis winding 51 are set as illustrated in FIG. 5A and FIG. 5E for making a straight connection between the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 , to perform the continuous non-inverting voltage supply.

In the time periods T 2 and T 6 , the first control signals G 1 a to G 4 b for the non-inverting voltage supply through the PWM control are generated.

The control signal generating unit 24 determines the time period T 2 as the current period based on 0<ref 1 <in (condition 2), and determines the time period T 6 as the current period based on 0>ref 1 >in (condition 6).

Upon determination of the time period T 2 or T 6 , the control signal generating unit 24 sets the levels of the gate signals G 1 a to G 4 b in power feeding period T 2 a , T 6 a in the same manner as in the time period T 1 , T 5 . Each of the power feeding periods T 2 a and T 6 a mentioned here is a part of the PWM cycle.

The control signal generating unit 24 consecutively changes the lengths of the power feeding periods T 2 a and T 6 a so that the ratio of the power feeding period T 2 a , T 6 a to the PWM cycle equals the ratio of the instantaneous value of the first target voltage ref 1 to the instantaneous value of the input voltage in. In the example illustrated in FIG. 4 , the lengths of the power feeding periods T 2 a and T 6 a are gradually reduced, and become zero at the end of the time periods T 2 and T 6 .

Furthermore, the control signal generating unit 24 sets the gate signals G 1 a and G 1 b of SW 11 and the gate signals G 3 a and G 3 b of SW 13 to the ON level, and sets the gate signals G 1 a and G 2 b of SW 12 and the gate signals G 4 a and G 4 b of SW 14 to the OFF level in regeneration periods T 2 b and T 6 b , each of which is the remaining part of the PWM cycle.

According to such gate signals G 1 a to G 4 b , in the time periods T 2 a and T 6 a , the conduction states of SW 11 to SW 14 and the current path of the first axis winding 51 are set as illustrated in FIG. 5A and FIG. 5E for making a straight connection between the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 , to perform the non-inverting voltage supply. Furthermore, in the time periods T 2 a and T 6 a , the conduction states of SW 11 to SW 14 and the current path of the first axis winding 51 are set as illustrated in FIG. 5B and FIG. 5F for short-circuiting the pair of the first output terminals 6 and 7 , to perform power regeneration which allows circulation, within the matrix switch 32 , of a regenerative current from the first axis winding 51 . As a result, the non-inverting voltage supply through the PWM control (cyclical power feeding and regeneration) is performed in the time periods T 2 and T 6 .

In the time periods T 3 and T 7 , the gate signals G 1 a to G 4 b for the inverting voltage supply through the PWM control are generated.

The control signal generating unit 24 determines the time period T 3 as the current period based on 0>ref 1 >−in (condition 3), and determines the time period T 7 as the current period based on 0<ref 1 <−in (condition 7).

Upon determination of the time period T 3 or T 7 , the control signal generating unit 24 sets the gate signals G 1 a and G 1 b of SW 11 and the gate signals G 4 a and G 4 b of SW 14 to the ON level and sets the gate signals G 1 a and G 2 b of SW 12 and the gate signals G 3 a and G 3 b of SW 13 to the OFF level in power feeding period T 3 a , T 7 a each of which is a part of the PWM cycle.

The control signal generating unit 24 consecutively changes the lengths of the power feeding periods T 3 a and T 7 a so that the ratio of the power feeding period T 3 a , T 7 a to the PWM cycle equals the ratio of the instantaneous value of the first target voltage ref 1 to the instantaneous value of the input voltage in. In the example illustrated in FIG. 4 , the lengths of the power feeding periods T 3 a and T 7 a are zero at the beginning of the time periods T 3 and T 7 , and are gradually increased afterward.

Furthermore, in regeneration periods T 3 b and T 7 b , each of which is the remaining part of the PWM cycle, the control signal generating unit 24 sets the levels of the gate signals G 1 a to G 4 b in the same manner as in the time periods T 2 b and T 6 b , respectively.

According to such gate signals G 1 a to G 4 b , in the time periods T 3 a and T 7 a , the conduction states of SW 11 to SW 14 and the current path of the first axis winding 51 are set as illustrated in FIG. 5C and FIG. 5G for making a cross connection between the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 , to perform the inverting voltage supply. Furthermore, in the time periods T 3 b and T 7 b , the conduction states of SW 11 to SW 14 and the current path of the first axis winding 51 are set as illustrated in FIG. 5D and FIG. 5H for short-circuiting the pair of the first output terminals 6 and 7 , to perform power regeneration which allows circulation, within the matrix switch 32 , of a regenerative current from the first axis winding 51 . As a result, the inverting voltage supply through the PWM control (cyclical power feeding and regeneration) is performed in the time periods T 3 and T 7 .

In the time periods T 4 and T 8 , the gate signals G 1 a to G 4 b for the continuous inverting voltage supply are generated.

The control signal generating unit 24 determines the time period T 4 as the current period based on 0>−in≧ref 1 (condition 4), and determines the time period T 8 as the current period based on 0<−in≦ref 1 (condition 8).

Upon determination of the time period T 4 or T 8 , the control signal generating unit 24 sets the levels of the gate signals G 1 a to G 4 b in the same manner as in the time period T 3 a , T 7 a.

According to such gate signals G 1 a to G 4 b , in the time periods T 4 and T 8 , the conduction states of SW 11 to SW 14 and the current path of the first axis winding 51 are set as illustrated in FIG. 5C and FIG. 5G for making a cross connection between the pair of the input terminals 3 and 4 and the pair of the first output terminals 6 and 7 , to perform the continuous inverting voltage supply.

Hereinbefore, the operations of converting the input voltage in into the first-phase output voltage out 1 have been described above in detail. Such operations are also performed for the second phase and the third phase to convert the input voltage in into the second-phase output voltage out 2 and the third-phase output voltage out 3 according to the second target voltage ref 2 and the third target voltage ref 3 , respectively.

Especially when the PWM control is performed for converting the input voltage in into the first-phase output voltage out 1 , the second-phase output voltage out 2 , and the third-phase output voltage out 3 , the control signal generating unit 24 may generate the gate signals G 1 a to G 4 b , G 5 a to G 8 b , and G 9 a to G 12 b to avoid overlap of a time period in which the pair of the input terminals and the pair of the first output terminals are connected, a time period in which the pair of the input terminals and the pair of the second output terminals are connected, and a time period in which the pair of the input terminals and the pair of the third output terminals are connected.

According to the power conversion apparatus 1 and the power conversion method described above, it is possible to convert the input voltage which is a single-phase AC voltage into a three-phase AC voltage with high efficiency using the matrix switch, without requiring a direct voltage in between.

The three-phase AC voltage obtained by the conversion by the power conversion apparatus 1 is used for, for example, driving the three-phase motor 5 in which the first axis winding 51 , the second axis winding 52 , and the third axis winding 53 are not electrically connected. Neither the three-phase motor 5 nor the power conversion apparatus 1 includes a capacitor that reduces the lifespan and reliability of the apparatus. Thus, combining the three-phase motor 5 and the power conversion apparatus 1 produces a long-life and highly reliable motor system which does not include a capacitor that reduces the lifespan and reliability of the apparatus.

In the case of driving a three-phase motor, such as the three-phase motor 203 , within which the end points of the windings of the three axes are electrically connected, the single-phase to three-phase conversion by the power conversion apparatus 1 produces output voltages having a large amplitude compared to output voltages produced by a typical single-phase to three-phase conversion. That is to say, output voltages having a larger amplitude can be applied to the windings of the respective axes. Therefore, the following advantageous effects can also be obtained.

FIG. 6A is a graph illustrating an example of three-phase line voltages 602 , 603 , and 604 and an input voltage 601 in the case of driving, with output voltages obtained by a single-phase to three-phase conversion performed by a typical matrix converter, a three-phase motor within which the end points of the windings of the three axes are electrically connected. FIG. 6B is a graph illustrating an example of the three-phase line voltages 602 , 603 , and 604 and the input voltage 601 in the case of driving, with output voltages obtained by a single-phase to three-phase conversion performed by the power conversion apparatus 1 , a three-phase motor within which the end points of the windings of the three axes are electrically connected. FIG. 6A and FIG. 6B illustrate line voltages obtained by converting input voltages having the same amplitude.

It was found that the amplitudes of the line voltages obtained by the power conversion apparatus 1 illustrated in FIG. 6B are approximately twice the amplitudes of the output voltages obtained by the single-phase to three-phase conversion performed by the typical matrix converter illustrated in FIG. 6A . This means that when driving a three-phase motor with the output voltages of the power conversion apparatus 1 , a torque is generated which is approximately twice the torque generated when driving the same three-phase motor with the output voltages of the typical matrix converter.

Thus, if the torque and the volume of the motor (e.g., amount of windings) are in proportion to each other, the same torque as that generated when driving a three-phase motor using the typical matrix converter can be generated by driving, using the power conversion apparatus 1 , a three-phase motor having a volume approximately ½ (approximately 50%) of that of the three-phase motor driven by the typical matrix converter.

Introducing a vector control function to the motor system combining the power conversion apparatus 1 and the three-phase motor 5 described above produces a motor system with higher controllability. The following describes such a motor system.

FIG. 7 is a block diagram illustrating an example of a functional configuration of another motor system according to Embodiment 1.

In the motor system illustrated in FIG. 7 , the three-phase motor 5 includes a rotation angle sensor 27 which outputs a rotation angle signal indicating consecutive rotation amounts of the rotor. A power conversion apparatus 1 a is different from the above-described power conversion apparatus 1 in that the power conversion apparatus 1 a includes, in a switch controller 26 a , a rotation angle obtaining unit 29 and a target voltage designating unit 23 a different from the target voltage designating unit 23 .

The rotation angle obtaining unit 29 obtains the rotation angle signal output from the rotation angle sensor 27 . The target voltage designating unit 23 a performs vector control to change at least one of the amplitude, frequency, and phase of the first target voltage ref 1 , the second target voltage ref 2 , and the third target voltage ref 3 based on a difference between a rotation speed of the rotor determined from the obtained rotation angle signal and a speed command value.

The vector control is specifically maintaining of the excitation current component of the winding current at a constant level, and regulation of the torque current component of the winding current.

The power conversion apparatus 1 a having the above configuration can control the rotation speed of the rotor by reducing the fluctuations in the rotation speed caused by load fluctuations.

FIG. 8 is a block diagram illustrating an example of a functional configuration of another motor system according to Embodiment 1.

The motor system illustrated in FIG. 8 includes a power conversion apparatus 1 b which is different from the above-described power conversion apparatus 1 in that the power conversion apparatus 1 b includes current sensors 30 a , 30 b , and 30 c , and also includes, in a switch controller 26 b , a current amount obtaining unit 31 and a target voltage designating unit 23 b different from the target voltage designating unit 23 .

The current sensor 30 a is a sensor which outputs a current amount signal indicating consecutive current amounts flowing in the pair of the first output terminals 6 and 7 . The current sensor 30 b is a sensor which outputs a current amount signal indicating consecutive current amounts flowing in the pair of the second output terminals 8 and 9 . The current sensor 30 c is a sensor which outputs a current amount signal indicating consecutive current amounts flowing in the pair of the third output terminals 10 and 33 . The current sensors 30 a , 30 b , and 30 c may be shunt resistors, for example. The current amount obtaining unit 31 obtains the signals output from the current sensors 30 a , 30 b , and 30 c.

The target voltage designating unit 23 b performs speed sensorless vector control to estimate the rotation speed of the rotor using the obtained consecutive current amounts, and change at least one of the amplitude, frequency, and phase of the first target voltage ref 1 , the second target voltage ref 2 , and the third target voltage ref 3 based on a difference between the estimated rotation speed and a speed command value.

With the speed sensorless vector control, the rotation speed of the rotor is estimated using a measured value of the winding current, and the torque is controlled using the estimated rotation speed. Since the rotation angle sensor likely to be subject to a constraint on its use environment is not used, the power conversion apparatus 1 b is suitable for controlling a motor used in a severe environment (e.g., where large vibrations are present).

The power conversion apparatus 1 b having the above configuration can control the rotation speed of the rotor by reducing the fluctuations in the rotation speed without using the rotation angle sensor.

The following describes that the same power conversion method as that described above can be applied even to a case where the amplitude, frequency, or phase of the first target voltage ref 1 , the second target voltage ref 2 , and the third target voltage ref 3 is changed.

FIG. 9 is a timing chart illustrating the waveform of each signal in the case where the above-described power conversion method is performed using a first target voltage ref 1 having a frequency three times greater than that of the first target voltage ref 1 illustrated in FIG. 4 , as an example of the case of changing the frequency. FIG. 9 is illustrated in the same manner as FIG. 4 .

FIG. 9 illustrates that even when the frequency of the first target voltage ref 1 is changed from FIG. 4 , it is still possible to determine the time periods T 1 to T 8 based on the same conditions as in FIG. 4 and generate the gate signals G 1 a to G 4 b according to the first target voltage ref 1 having a higher frequency. This holds true for the case of changing the amplitude or phase of the first target voltage ref 1 .

Variations of Embodiment 1

In the above embodiment, the state of each of the bidirectional switches 11 to 14 is changed to either a bidirectional conducting state or a non-conducting state, using the gate signals having the same waveform for the two unidirectional switches forming the bidirectional switch. Thus, the levels of two gate signals are constantly changed at the same time for each bidirectional switch, thereby increasing the total number of times the levels of the gate signals are changed. Thus, the levels of two gate signals are constantly changed at the same time for each bidirectional switch, thereby increasing the total number of times the levels of the gate signals are changed. This results in relatively large power consumption for the switching operation (including the gate signal generation, the charge and discharge of the signal lines, and the charge and discharge of the gate capacitance of the unidirectional switches). Such an increase in the power consumption is noticeable especially in the non-inverting voltage supply performed through the PWM control and in the inverting voltage supply performed through the PWM control.

To overcome this, the power required for driving the gate signals can be reduced by fixing the level of the gate signal corresponding to one of the unidirectional switches included in one bidirectional switch. The following describes two variations for generating such gate signals.

In Variation 1, the gate signals G 1 a to G 8 b are generated to change between the conducting state and the non-conducting state of only one of the two unidirectional switches included in one bidirectional switch, to which the input voltage in is applied in the forward direction, and to constantly place, in the conducting state, the other of the two unidirectional switches to which the input voltage in is applied in the opposite direction.

FIG. 10 is a timing chart illustrating an example of the waveforms of the gate signals G 1 a to G 4 b generated based on the above idea. FIG. 10 is illustrated in the same manner as FIG. 4 , and the waveform of each gate signal is distinguishably shown for the corresponding unidirectional switch. Specifically, the waveform of each gate signal (having a reference sign with “a” at the end) of the unidirectional switch illustrated on the left (in the drawing) in the corresponding bidirectional switch is shown with a solid line, whereas the waveform of each gate signal (having a reference sign with “b” at the end) of the unidirectional switch illustrated on the right (in the drawing) in the corresponding bidirectional switch is shown with a dotted line.

FIG. 11A to FIG. 11H are circuit diagrams each illustrating: the conduction states of SW 11 to SW 14 that are set according to the gate signals G 1 a to G 4 b illustrated in FIG. 10 in the time periods T 1 to T 8 ; and the current path of the first axis winding 51 determined accordingly. FIG. 11A to FIG. 11H are illustrated in the same manner as FIG. 5A to FIG. 5H .

The gate signals G 1 a to G 4 b in FIG. 10 are different from the gate signals G 1 a to G 4 b in FIG. 4 in the following points:

Specifically, the gate signals G 1 a , G 2 b , G 3 a , and G 4 b are fixed at the ON level to constantly place, in the conducting state, the unidirectional switches to which the input voltage in is applied in the opposite direction in the time periods T 1 to T 4 , namely, the left unidirectional switch of SW 11 , the right unidirectional switch of SW 12 , the left unidirectional switch of SW 13 , and the right unidirectional switch of SW 14 .

Furthermore, the gate signals G 1 b , G 2 a , G 3 b , and G 4 a are fixed at the ON level to constantly place, in the conducting state, the unidirectional switches to which the input voltage in is applied in the opposite direction in the time periods T 5 to T 8 , namely, the right unidirectional switch of SW 11 , the left unidirectional switch of SW 12 , the right unidirectional switch of SW 13 , and the left unidirectional switch of SW 14 .

Moreover, the gate signals G 1 b , G 3 b , G 1 a , and G 3 a are fixed at the OFF level to constantly place, in the non-conducting state, the unidirectional switches which are in a direction opposite to the regenerative current from the first axis winding 51 in the time periods T 2 , T 3 , T 6 , and T 7 , namely, the right unidirectional switch of SW 11 in the time period T 2 , the right unidirectional switch of SW 13 in the time period T 3 , the left unidirectional switch of SW 11 in the time period T 6 , and the left unidirectional switch of SW 13 in the time period T 7 .

With the gate signals G 1 a to G 4 b in FIG. 10 , the same switching operations as in the case of the gate signals G 1 a to G 4 b in FIG. 4 are performed as illustrated in FIG. 11A to FIG. 11H . The gate signals the levels of which change for the PWM control are only the gate signals G 2 a , G 4 a , G 2 b , G 4 b in the time periods T 2 , T 3 , T 6 , and T 7 . This significantly reduces the total number of times the levels of the gate signals are changed, and thus decreases the amount of power required for driving the gate signals.

In general, with a power conversion apparatus which drives an inductive load, after the polarity of the power supply voltage is inverted, the regenerative current from the load sometimes continues to flow in the same direction as the direction prior to the inversion of the polarity of the power supply voltage, especially when the inductance of the load is large, for example.

When this is considered in relation to the above-described motor system, it means that there are cases where the regenerative current from the first axis winding 51 illustrated in FIG. 11A and FIG. 11B flows in a direction opposite to the illustrated direction, for example. Such opposite flow occurs when a large magnetic energy accumulated in the preceding period is remaining in the first axis winding 51 .

When the regenerative current from the first axis winding 51 flows in the direction opposite to the illustrated direction, the regenerative current from the first axis winding 51 circulates to the single-phase AC power supply 2 in the case of FIG. 11A , whereas in the case of FIG. 11B , there is no path along which the regenerative current can circulate, and thus an extremely large voltage is applied to SW 11 and a large power loss occurs.

To solve such a problem, Variation 2 provides a path of the regenerative current from the load by placing plural bidirectional switches in the bidirectional conducting state.

FIG. 12 is a timing chart illustrating an example of the waveforms of the gate signals G 1 a to G 4 b generated based on the above idea. FIG. 12 is illustrated in the same manner as FIG. 10 .

The gate signals G 1 a to G 4 b in FIG. 12 are different from the gate signals G 1 a to G 4 b in FIG. 10 in that the gate signals G 1 b , G 3 b , G 1 a , and G 3 a are set to the ON level in the time periods T 2 b , T 3 b , T 6 b , and T 7 b to form a path of the regenerative current from the first axis winding 51 via SW 11 and SW 13 placed in the bidirectional conducting state.

With the gate signals G 1 a to G 4 b in FIG. 12 , the same switching operations as in the case of the gate signals G 1 a to G 4 b in FIG. 4 are performed for the winding current flowing in the illustrated direction, as illustrated in FIG. 13A to FIG. 13H . In addition, in the time periods T 2 b , T 3 b , T 6 b , and T 7 b , the path of the regenerative current from the first axis winding 51 is formed via SW 11 and SW 13 placed in the bidirectional conducting state, and thus it is possible to pass the regenerative current in the direction opposite to the illustrated direction.

This results in an increase in the total number of times the levels of the gate signals are changed because not only the levels of the gate signals G 2 a , G 4 a , G 2 b , and G 4 b but also the levels of the gate signals G 1 b , G 3 b , G 1 a , and G 3 a are changed in the PWM control. However, it becomes possible to allow the regenerative current from the first axis winding 51 to circulate within the matrix switch 32 irrespective of the direction of the regenerative current, and thus power regeneration can be appropriately performed.

First, the following describes a power conversion method for making the output voltage zero (suspending the voltage supply) during a time period in which the absolute value of the input voltage is insufficient.

FIG. 14 and FIG. 15 are timing charts each illustrating an example of the waveforms of the gate signals G 1 a to G 4 b generated by the control signal generating unit 24 for performing such a power conversion method. The gate signals G 1 a to G 4 b in FIG. 14 and FIG. 15 are partly different from the gate signals G 1 a to G 4 b in FIG. 10 and FIG. 12 , respectively.

The gate signals G 1 a to G 4 b in FIG. 14 are different from the gate signals G 1 a to G 4 b in FIG. 10 only in that the gate signals G 2 a , G 4 a , G 2 b , and G 4 b are fixed at the OFF level in the time periods T 1 , T 4 , T 5 , and T 8 in which the instantaneous absolute value of the input voltage in is less than or equal to the instantaneous absolute value of the first target voltage ref 1 . In other words, in the time periods T 1 , T 4 , T 5 , and T 8 , the gate signals G 1 a to G 4 b in FIG. 14 are set at the same levels as those in the time periods T 2 b , T 3 b , T 6 b , and T 7 b , respectively, each of which is a regeneration period of the PWM cycle. As a result, the voltage supply is suspended and the first-phase output voltage out 1 becomes zero.

With the gate signals G 1 a to G 4 b in FIG. 14 , in the time periods T 1 , T 4 , T 5 , and T 8 , the conduction states of SW 11 to SW 14 and the current path of the first axis winding 51 are set as illustrated in FIG. 11B , FIG. 11D , FIG. 11F , and FIG. 11H , respectively, and power regeneration is performed allowing the regenerative current from the first axis winding 51 to circulate within the matrix switch 32 .

The gate signals G 1 a to G 4 b in FIG. 15 are different from the gate signals G 1 a to G 4 b in FIG. 12 only in that the gate signals G 2 a , G 4 a , G 2 b , and G 4 b are fixed at the OFF level and the gate signals G 1 b , G 3 b , G 1 a , and G 3 a are fixed at the ON level in the time periods T 1 , T 4 , T 5 , and T 8 in which the instantaneous absolute value of the input voltage in is less than or equal to the instantaneous absolute value of the first target voltage ref 1 . In other words, in the time periods T 1 , T 4 , T 5 , and T 8 , the gate signals G 1 a to G 4 b in FIG. 15 are set at the same levels as those in the time periods T 2 b , T 3 b , T 6 b , and T 7 b , respectively, each of which is a regeneration period of the PWM cycle. As a result, the voltage supply is suspended and the first-phase output voltage outs becomes zero.

With the gate signals G 1 a to G 4 b in FIG. 15 , in the time periods T 1 , T 4 , T 5 , and T 8 , the conduction states of SW 11 to SW 14 and the current path of the first axis winding 51 are set as illustrated in FIG. 13B , FIG. 13D , FIG. 13F , and FIG. 13H , respectively, and power regeneration is performed allowing the regenerative current from the first axis winding 51 to circulate within the matrix switch 32 .

According to the power conversion method described above, the voltage supply is suspended by making the output voltage zero during the time period in which the absolute value of the input voltage is insufficient. Thus, the fluctuations of the input voltage can be reduced without placing an excessive load on the power supply (including the resistance of a wire, for example) that supplies the input voltage. Furthermore, since there is no longer a need to accurately estimate the time at which the input voltage becomes 0 V, misoperation is less likely to occur even when the circuit illustrated in FIG. 1A having few sensors is used instead of the circuit illustrated in FIG. 1B capable of accurately calculating the potential difference of the input voltage.

Next, the following describes a power conversion method for leveling out, among a plurality of bidirectional switches, the number of times switching is performed.

FIG. 16 is a timing chart illustrating an example of the waveforms of the gate signals G 1 a to G 4 b generated by the control signal generating unit 24 for performing such a power conversion method. The gate signals G 1 a to G 4 b in FIG. 16 are partly different from the gate signals G 1 a to G 4 b in FIG. 14 .

The gate signals G 1 a to G 4 b in FIG. 16 are different from the gate signals G 1 a to G 4 b in FIG. 14 only in that in the time periods T 5 and T 6 , the changing of the level of the gate signal G 2 a is stopped and the level of the gate signal G 3 a is changed instead, and in the time periods T 7 and T 8 , the changing of the level of the gate signal G 4 b is stopped and the level of the gate signal G 1 a is changed instead.

FIG. 17A to FIG. 17D are circuit diagrams each illustrating: the conduction states of the bidirectional switches 11 to 14 that are set according to the first control signals G 1 a to G 4 b illustrated in FIG. 16 in the time periods T 5 to T 8 ; and the current path of the first axis winding 51 determined accordingly.

With the gate signals G 1 a to G 4 b in FIG. 16 , the conduction states of SW 11 to SW 14 and the current path of the first axis winding 51 are set as illustrated in FIG. 17A , FIG. 17B , FIG. 17C , and FIG. 17D in the time period T 6 a , the time periods T 5 and T 6 b , the time period T 7 a , and the time periods T 7 b and T 8 , respectively.

As a result, the non-inverting voltage supply through the PWM control (cyclical power feeding and regeneration) is performed through the switching operations of SW 12 and SW 13 which differ between the time periods T 2 and T 6 , and the inverting voltage supply through the PWM control (cyclical power feeding and regeneration) is performed through the switching operations of SW 14 and SW 11 which differ between the time periods T 3 and T 7 .

According to the power conversion method described above, leveling out the number of times of the switching operations of the bidirectional switches 11 to 14 leads to leveling out of the heat generated by the bidirectional switches 11 to 14 . As a result, it is possible to reduce the disadvantages of decreased rated power and lower reliability caused by local overheating of the bidirectional switches 11 to 14 .

The power conversion method for leveling out the number of times of the switching operations of the bidirectional switches 11 to 14 can be combined with the power conversion method for providing the path of the regenerative current from the load by placing plural bidirectional switches in the bidirectional conducting state.

FIG. 18 is a timing chart illustrating an example of the waveforms of the gate signals G 1 a to G 4 b generated by the control signal generating unit 24 for performing such a power conversion method. The gate signals G 1 a to G 4 b in FIG. 18 are partly different from the gate signals G 1 a to G 4 b in FIG. 16 .

The gate signals G 1 a to G 4 b in FIG. 18 are different from the gate signals G 1 a to G 4 b in FIG. 16 in that in the time periods T 2 b and T 3 b , the gate signals G 1 b and G 3 b are set at the ON level to form a path of the regenerative current from the first axis winding 51 via SW 11 and SW 13 placed in the bidirectional conducting state, and in the time periods T 6 b and T 7 b , the gate signals G 4 b and G 2 b are set at the ON level to form a path of the regenerative current from the first axis winding 51 via SW 12 and SW 14 placed in the bidirectional conducting state.

With the gate signals G 1 a to G 4 b in FIG. 18 , the same switching operations as in the case of the gate signals G 1 a to G 4 b in FIG. 4 can be performed as illustrated in FIG. 19A to FIG. 19H . In addition, in the time periods T 2 b and T 3 b , the path of the regenerative current from the first axis winding 51 is formed via SW 11 and SW 13 placed in the bidirectional conducting state, and in the time periods T 6 b and T 7 b , the path of the regenerative current from the first axis winding 51 is formed via SW 12 and SW 14 placed in the bidirectional conducting state.

As a result, it becomes possible to level out the number of times of the switching operations of the bidirectional switches 11 to 14 and to allow the regenerative current from the first axis winding 51 to circulate within the matrix switch 32 irrespective of the direction of the regenerative current.

Although only some exemplary embodiments of the power conversion apparatus according to the present invention have been described in detail above, those skilled in the art will readily appreciate that many modifications are possible in the exemplary embodiments, such as an embodiment conceived by combining the structural elements of two or more of the above-described embodiments, without materially departing from the novel teachings and advantages of the present invention. Accordingly, all such modifications are intended to be included within the scope of the present invention.

The present disclosure is applicable to a power conversion apparatus which converts a single-phase AC voltage into a three-phase AC voltage, and can be used especially for driving a three-phase motor.

1 , 1 a , 1 b Power conversion apparatus

2 Single-phase AC power supply

3 , 4 Input terminal

5 Three-phase motor

6 , 7 First output terminal

8 , 9 Second output terminal

10 , 33 Third output terminal

11 , 12 , 13 , 14 First bidirectional switch

15 , 16 , 17 , 18 Second bidirectional switch

19 , 20 , 21 , 22 Third bidirectional switch

23 , 23 a , 23 b Target voltage designating unit

24 Control signal generating unit

25 Driver

26 , 26 a , 26 b Switch controller

27 Rotation angle sensor

29 Rotation angle obtaining unit

30 a , 30 b , 30 c Current sensor

31 Current amount obtaining unit

32 Matrix switch

51 First axis winding

52 Second axis winding

53 Third axis winding

54 Rotor

56 , 57 First power receiving terminal

58 , 59 Second power receiving terminal

60 , 61 Third power receiving terminal

200 Matrix converter

201 Single-phase AC power supply

202 a , 202 b , 202 c , 202 d , 202 e , 202 f Bidirectional switch

203 Three-phase motor

204 Magnitude determining unit

205 Control unit

M 1 , M 2 , M 3 , M 4 IGBT

M 5 GaN HFET

D 1 , D 2 Diode

G 1 a , G 1 b , G 2 a , G 2 b , G 3 a , G 3 b , G 4 a , G 4 b First control signal (Gate signal)

G 5 a , G 5 b , G 6 a , G 6 b , G 7 a , G 7 b , G 8 a , G 8 b Second control signal (Gate signal)

G 9 a , G 9 b , G 10 a , G 10 b , G 11 a , G 11 b , G 12 a , G 12 b Third control signal (Gate signal)

601 Input voltage

602 Line voltage (between first axis voltage and second axis voltage)

603 Line voltage (between second axis voltage and third axis voltage)

604 Line voltage (between third axis voltage and first axis voltage)