Systems methods and computer program products for generating and optimizing signal constellations

The present application is related to and claims priority from U.S. Provisional Application Serial No. 60/134,997, entitled APPARATUS, METHOD AND COMPUTER PROGRAM PRODUCT FOR GENERATING AND OPTIMIZING SIGNAL CONSTELLATIONS filed May 20, 1999, the disclosure of which is incorporated herein by reference as if set forth fully herein.

This application is related to U.S. application Ser. No. 09/264,085, entitled RECEIVERS, METHODS, AND COMPUTER PROGRAM PRODUCTS FOR AN ANALOG MODEM THAT RECEIVES DATA SIGNALS FROM A DIGITAL MODEM (Docket No. RA9-98-074), U.S. application Ser. No. 09/264,272, entitled MODEMS, METHODS, AND COMPUTER PROGRAM PRODUCTS FOR IDENTIFYING A SIGNALING ALPHABET IN VARIANCE WITH AN IDEAL ALPHABET DUE TO DIGITAL IMPAIRMENTS (Docket No. RA9-98-075), U.S. application Ser. No. 09/264,475, entitled MODEMS, METHODS, AND COMPUTER PROGRAM PRODUCTS FOR SELECTING AN OPTIMUM DA TA RATE USING ERROR SIGNALS REPRESENTING THE DIFFERENCE BETWEEN THE OUTPUT OF AN EQUALIZER AND THE OUTPUT OFA SLICER OR DETECTOR (Docket No. RA9-98-077), which are incorporated herein by reference.

The present invention relates generally to the field of modems, and, more particularly, to the construction and optimization of signal constellations for data transmission based on available signal alphabets that are either known a priori, determined through identification of model parameters, or estimated during modem start-up by means of learning techniques.

Although the preferred embodiment will be described with respect to a pulse code modulation (PCM) modem, the present invention is in no way limited to PCM type modems and may be used with non-PCM modems. The present invention relates to the construction and optimization of signal constellations for the downlink of a PCM modem communication, system. The communications channel of interest for PCM modems is shown in FIG. 1. A digital modem 10 is connected to the digital transport 20 , which is connected by means of a D/A converter 30 in a PCM codec 40 to the subscriber line 50 . An analog modem 60 is connected to the opposite end of the subscriber line 50 .

PCM modems such as modems according to ITU-T Recommendation V.90 employ pulse-amplitude modulation (PAM) for downstream signaling, where the signal constellations are sets of PCM codes according to the ITU-T Recommendation G.711 transmitted by the digital modem and corresponding voltage levels, at a given point of reference. Unless specified otherwise, the point of reference will be the output of the D/A converter 30 in the PCM codec 40 , which is typically located at the Central Office.

For downstream data transmission according to Recommendation V.90, data bits are mapped to PCM codes according to Recommendation G.711 by the digital modem. The PCM codes are sent through the digital network and converted to analog voltage levels by the D/A converter in the PCM codec 40 of the Central Office. In mu-law networks, robbed-bit signaling (RBS) is often used for in-band call control, which results in the least-significant bit of a PCM code being unavailable for PCM modem data transmission. Moreover, digital attenuation pads with numerous attenuation levels and implementation characteristics are employed in the digital network. Both RBS and digital attenuation pads act as impairments from the perspective of PCM modem data transmission.

Due to the frame structure present on digital T 1 links, a frame size of 6 modulation intervals T (6 samples at 8000 samples/second) was selected for downstream data transmission in V.90. Generally, the combination of impairments, such as RBS, digital pads, and PCM codec infidelity, may be different for each interval of a 6T frame. Since certain clusters of PCM codes are mapped by the digital impairments to the same PCM code, only a subset of non-overlapping PCM codes (with one representative from each cluster) can be used for data signaling in any of the 6 intervals, and the 6 subsets are generally different. Recomnnendation G.711 specifies the voltage levels at the D/A converter output corresponding to the 256 PCM codes. However, the subset of these PCM codes that is actually used is not known in advance. Moreover, the true voltage levels corresponding to these remaining PCM codes may differ significantly from the ideal levels specified by G.711 due to PCM codec infidelity and other impairments.

The presence of a priori unknown impairments in both the digital network and the PCM codec may require precise identification of the voltage levels corresponding to transmitted PCM codes, independently for each interval of a frame (cf. related U.S. application Ser. No. 09/264,272). The Recommendation V.90 uses a frame size of 6 modulation symbols, at a rate of 8000 symbols/second. In V.90 start-up, for example, this identification can be accomplished by the analog modem by using the DIL (Digital Impairment Learning) sequence of Phase 3 of the startup procedure. After an initial training of the analog modem's equalizer (cf. related U.S. application Ser. No. 09/264,085), the voltage levels (i.e. signal levels) corresponding to transmitted PCM codes are learned separately for each interval in a frame of 6 modulation intervals.

The V.90 Recommendation allows up to 6 different signal constellations, which may be selected and assigned to intervals of a data frame by the analog modem. These constellations may be selected with a suitable spacing between adjacent signal levels to allow for reliable data transmission in the presence of noise and other distortions while maximizing the data rate subject to a constraint on average power. In practice, reliability is specified in terms of a desired probability of symbol error.

A significant constraint may be the power limit as well as the point of reference for measuring power imposed by country-specific regulations. The power limit and point of reference are sent by the digital modem to the analog modem during V.90 start-up. If the point of reference is at the output of the PCM codec and the presence of digital pads is detected, the analog modem can compensate for the attenuation and achieve higher data rates.

The problem of constellation generation in a V.90 modem is made significantly more difficult by the wide range of PCM-modem specific impairments under which near-optimal constellations must be selected. Another complication is that the impairments encountered for a particular connection may be unpredictable and may change from call to call. Furthermore, a V.90 modem may have only a limited amount of time available during start-up for selecting optimal signal constellations.

The problem of constellation generation for PCM modems was described in a TR-30.1 contribution by R. Fischer and G. Ungerboeck. However, no practical solution for solving the optimization problem with finite computational resources was proposed. Also, in U.S. Pat. No. 5,831,561 (hereinafter “the '561 patent”), the use of learned levels as the source of a signaling alphabet is described. However, little detail is provided as to how to build a constellation other than by selecting a larger number of available points and then reducing the number of points to the desired number of points by optimizing the minimum distance between points. Thus, the '561 patent assumes a first data rate and then finds an achievable data rate based on the assumed data rate. The assumption of a first data rate is not necessary in the present invention.

Certain objects, advantages, and features of the invention will be set forth in the description that follows and will become apparent to those skilled in the art upon examination of the following or may be learned with the practice of the invention.

It is an object of the present invention to provide an improved method for the selection and optimization of a set of signal constellations for data transmission.

It is another object of the present invention that it can be used in a V.90 client or other PCM modem to select a set of signal constellations for downstream data transmission.

It is yet another object of the present invention to allow for the selection of near-optimal signal constellations as subsets of available signal alphabets. Specifically, for PCM modem channels, the available signal alphabets are dependent on the digital impairments encountered in a particular modem connection.

Another object of the present invention is to reduce or eliminate dependencies on a precise model of the impairments in the digital network and the PCM codec in constellation generation.

A further object of the present invention is to automatically take into account the effect of impairments for a wide range of PCM-modem specific impairments.

Another object of the present invention is to provide flexibility in selecting the signal constellations for different power limits and target error probabilities.

These and other objects of the present invention may be provided by methods, systems and computer program products for constellation generation which determine the range of available and usable ucodes and an initial minimum spacing between signal levels. A work constellation set is generated based on the initial range of ucodes and the initial minimum signal level spacing. The work constellation set is then iteratively adjusted so as to provide a work constellation set which achieves an error probability target. The work constellation set is then iteratively pruned so as to provide a pruned work constellation set which achieves a power limit. The pruned work constellation set is then iteratively fine-tuned so as to provide a final constellation set which is within a specified tolerance of the error probability target and/or the power limit.

In a further embodiment, the power limit may be enforced utilizing an exact distribution of the final constellation. Furthermore, the initial minimum signal level spacing may be determined based on mean squared error and a target symbol error probability.

In a particular embodiment of the present invention, the work constellation set is iteratively adjusted by reducing the minimum signal level spacing in order to approximate a target symbol error probability. Such an iterative reduction may be achieved by iteratively reducing the minimum signal level spacing until the symbol error probability of the work constellation set slightly exceeds a target symbol error probability. Furthermore, the minimum signal level spacing may finally be set to a value between a first minimum signal level spacing which results in a work constellation set with a symbol error probability below the target symbol error probability and the minimum signal level spacing which results in the symbol error probability of the work constellation set slightly exceeding the target symbol error probability.

In another embodiment of the present invention, the work constellation set is iteratively pruned by eliminating a largest signal level from the work constellation set. The iterative elimination of the largest signal level in the work constellation set is repeated until a constellation power below the power limit is reached.

In still another embodiment of the present invention, the work constellation set is iteratively fine-tuned by increasing the minimum signal level spacing until the constellation power of the resulting work constellation set is within a threshold value of the power limit. Furthermore, the multiplicity of signal levels which are at the minimum spacing with respect to a neighboring signal level, may also be reduced to fine-tune the work constellation set.

In preferred embodiments of the present invention, the work constellation sets at different stages of the described optimization have a signal-point distribution that is close to uniform, simplifying the computation of average power or symbol error probability.

In still another embodiment of the present invention, the initial minimum signal level spacing is established as a function of mean squared error.

In particular embodiments of the present invention, the minimum signal level spacing is reduced by determining d min , LB = min 0 ≤ i ≤ 5  min  ( 2  c i , 0 ′ , c i , 1 ′ - c i , 0 )

where d min,LB is the minimum signal level spacing and c′ i0 and c′ i1 are reduced smallest and second smallest signal levels and c i,0 is a previous smallest signal level of the work constellation set and wherein i is a frame interval. Furthermore, the largest level which is pruned may be the largest level satisfying (M i −1)(P−Q)≧Q, wherein M i is a number of levels being used in a frame interval i, P is the product of all the M i values and Q is 2 K where K=└log 2 (P)┘.

If the attenuation due to digital pads in the network is known, the present invention may benefit from this knowledge by taking it into account in the computation of average power. Moreover, the present invention may provide fine control on how closely the power limit or error probability target are approximated. The present invention also is memory efficient as large tables of parameters corresponding to a wide range of impairments as well as input parameters are not required.

Preferably, the iterative operations are partitioned into submethods for flexibility and to allow a computationally efficient implementation. One submethod may allow an efficient selection of the minimal spacing between signal levels to approximate the target symbol error rate. Another submethod may be used for pruning the work constellations in order to meet the power constraint. Yet another submethod may be used for efficiently modifying the work constellations to approach the power limit more closely, e.g., by increasing the minimal spacing between signal levels, or by not selecting some of the signal levels that are at the minimal spacing.

Other features of the present invention will be more readily understood from the following detailed description of specific embodiments thereof when read in conjunction with the accompanying drawings, in which:

FIG. 1 is a block diagram showing the PCM modem communication channel in accordance with the prior art;

FIG. 2 illustrates a technique for reducing the minimum spacing between levels in accordance with the learned DIL levels; and

FIG. 3 is a flow chart showing a typical sequence of steps for constellation generation according to the present invention.

The present invention will now be described more fully hereinafter with reference to the accompanying drawings, in which preferred embodiments of the invention are shown. This invention may, however, be embodied in different forms and should not be construed as limited to the embodiments set forth herein. Rather, these embodiments are provided so that this disclosure will be thorough and complete, and will fully convey the scope of the invention to those skilled in the art. Like reference numbers signify like elements throughout the description of the figures.

The present invention may be embodied as a system, a method, or a computer program product. Accordingly, the present invention may take the form of an entirely hardware embodiment, an entirely software (including firmware, resident software, micro-code, etc.) embodiment, or an embodiment containing both software and hardware aspects. Furthermore, the present invention may take the form of a computer program product on a computer-usable or computer-readable storage medium having computer-usable program code means embodied in the medium for use by or in connection with an instruction execution system. In the context of this document, a computer-usable or computer-readable medium may be any means that can contain, store, communicate, propagate, or transport the program for use by or in connection with the instruction execution system, apparatus, or device.

The computer-usable or computer-readable medium may be, for example but not limited to, an electronic, magnetic, optical, electromagnetic, infrared, or semiconductor system, apparatus, device, or propagation medium. More specific examples (a nonexhaustive list) of the computer-readable medium would include the following: an electrical connection having one or more wires, a portable computer diskette, a random access memory (RAM), a read-only memory (ROM), an erasable programmable read-only memory (EPROM or Flash memory), an optical fiber, and a portable compact disc read-only memory (CD-ROM). Note that the computer-usable or computer-readable medium could even be paper or another suitable medium upon which the program is printed, as the program can be electronically captured, via, for instance, optical scanning of the paper or other medium, then compiled, interpreted or otherwise processed in a suitable manner if necessary, and then stored in a computer memory.

Computer program code for carrying out operations of the present invention may be written in a high level programming language such as C or C++. Some modules or routines, however, may be written in assembly language, machine language, or micro-code to optimize speed, memory usage, or layout of the software or firmware in memory. In a preferred embodiment, the present invention uses micro-code to implement most software programs. It should further be understood that the program code for carrying out operations of the present invention may also execute entirely on a client modem, partly on a client modem, partly on a client modem and partly on a server modem, or partly in a client modem, partly in a server modem, and partly in the PSTN.

PCM Modem Preliminaries

The V.90 Recommendation defines universal codes (ucodes), which allow an identical description of the downstream encoder regardless of whether A-law or mu-law codes are presented at the network interface of the digital PCM modem. There are 128 ucodes, which represent the 128 nonnegative voltage levels according to the ITU-T Recommendation G.711. Given a particular PCM coding law, a ucode together with a sign bit defines the PCM code sent by the digital modem. For simplicity, the digital PCM modem can therefore be assumed to send ucodes.

In every 6T frame, blocks of K data bits are encoded by the digital PCM modem into a sequence of 6 indices m i ,i=0 . . . 5, through a technique called modulus encoding. These indices satisfy 0≦m i <M i , where M, denotes the modulus, i.e., the number of voltage levels being used in interval i. In a notation convenient for the presentation of the subject invention, the modulus encoding specified in the V.90 Recommendation can be stated as follows:

1. Represent the incoming K bits as an integer r 0 =b 0 +b 1 2+b 2 2 2 +. . . b K−1 2 K−1.

2. Divide r 0 by M 0 . The remainder of this division gives m 0 , the quotient becomes r 1 for the next interval. Continue for the remaining five intervals i=1 . . . 5 as follows. According to Euclid's integer division theorem, there are unique numbers r i+1 and m i such that r i =M i r i+1+m i , where 0<m i <M i . These numbers can be written as

m i =r i mod M i   EQ.1

r i+1 =└r i /M i ┘=( r i −m i )/i M i .  EQ.2

Note that the modulus encoding is invertible if, and only if, the condition 2 K ≤ ∏ i = 0 S     Mi EQ .    3

is satisfied.

Referring to the subset of non-overlapping ucodes and corresponding nonnegative voltage levels in any interval i as the available signal alphabet of interval i. Note that the available signal alphabets are not known a priori to the analog PCM modem.

The objective of the disclosed constellation generation method is to select numbers M i , i=0 . . . 5, and signal constellations C i , i=0 . . . 5, subject to various optimization criteria, where each signal constellation is comprised of a set of ucodes and corresponding voltage levels.

Since the available signal alphabets are unknown a priori, there are two possible approaches for constellation generation, model-based constellation generation (MCG) and learning-based constellation generation (LCG). Constellation generation according to the present invention can be used for both LCG and MCG. However, due to the absence of a (necessarily incomplete) impairment model, LCG is the preferred approach for constellation generation.

In model based constellation generation, the mapping between transmitted ucodes and received signal levels is represented by a small set of parameters such as a pad attenuation and, for each of the 6 intervals, an RBS type parameter. The fundamental assumption is that the mapping can be exactly parameterized and that the set of values these parameters can take is finite and known. The analog PCM modem attempts to determine the model parameters from the received V.90 digital impairment learning (DIL) signal. These parameters are then used to obtain the voltage levels corresponding to the 128 ucodes. Such extrapolated voltage levels are then used as the basis for constellation generation. An advantage of MCG is the precision of the model-based voltage levels in the case where the model parameters are identified correctly, assuming perfect fidelity of the PCM codec. In this case, the available signal alphabets are known precisely, despite the noise present on the subscriber line. The main limitation of MCG is the possibility of false model parameter identification. If the model parameters do not precisely represent the mapping from transmitted ucodes to voltage levels, systematic errors in data transmission may occur. Based on practical experience, it is impractical to define a complete model of impairments and at the same time be able to identify the model parameters with an acceptably low probability of false identification.

In learning-based constellation generation, 6 DIL constellations are estimated during start-up by learning, as described by a related application (Ser. No. 09/264,272). The 6 learned DIL constellations are used as the basis for constellation generation. There is no dependency on a precise impairment model, i. e., the parameter-based extrapolation step is avoided.

In the following, {L i,n ,n=u min . . . u max } denotes the set of voltage levels corresponding to the ucodes u min . . . u max in interval i. The levels L i,n may result from learning using the V.90 DIL signal in the case of LCG or from the identification of model parameters in the case of MCG.

Constellation generation selects constellations as subsets of the sets {L i,n ,n=u min . . . u max }, taking into account the measured mean-squared error (MSE) or signal-to-noise ratio (SNR) at the equalizer output, the target symbol error probability, and other constraints.

A work constellation is a set of transmitted ucodes {u i,m (TX) } and corresponding levels {l i,m } for interval i, obtained by selecting a subset of {L i,n ,n=u min . . . u max } with distance between levels not less than a given lower bound on minimum distance, d min,LB and, optionally, satisfying additional constraints to reduce the multiplicity of levels which are at distance d min,LB from a neighbor, or to limit the modulus M i , i.e., the number of elements in the set {l,m}. The work constellations for all intervals is collectively referred to as a work constellation set.

Note that the minimum ucode u min,i and maximum ucode u max,i are selected based on various considerations such as available DIL levels, distortion at large or small DIL levels, etc. Note further that U min,i and u max,i may vary across intervals i and may also vary across different steps of the constellation generation algorithm.

During constellation generation in an analog V.90 modem, the subject invention constructs and optimizes a set of 6 work constellations simultaneously.

Submethods for Constellation Generation

A constellation generation method of the present invention may use several submethods as described in this section.

Generation of Work Constellations

In a preferred embodiment, the set of work constellations is fully specified by the parameters d min,LB , u min,i and u max,i . Note that the range of ucodes can be selected to limit the number of iterations in individual steps of the constellation generation method. By reducing the largest ucode it is possible to exclude large signal levels, which are more likely to be affected by nonlinear distortion.

Efficient Selection of d min,LB

During constellation generation, there may be cases where d min,LB needs to be decreased or increased to better approximate the given constraints. During a modem start-up, it may be computationally impractical to exhaustively search for the best value of d min,LB in terms of approximating the desired operating point.

One example situation where d min,LB may be reduced iteratively is at the beginning of constellation generation, where an initial set of work constellations is constructed based on a conservatively high value d 0 min,LB . The initial lower bound is then reduced to a value d min,LB by applying a small correction that is guaranteed to change the set of work constellations. (Note that an arbitrary, small reduction of the lower bound on minimum distance could still give rise to the same achieved minimum distance as before, in which case the set of work constellations would not change and computational resources would be wasted.) Let the smallest and second-smallest signal levels of a work constellation for interval i be denoted by c i,0 and c i,1 , respectively, which are elements of the set {L i,n n=u min . . . u max }. Considering that, in most cases, the minimum distance between any two points in a constellation is either the distance between the smallest level and the negative of the smallest level or the distance between the two smallest levels, a smaller minimum distance can be obtained by replacing either c i,0 with c′ i,0 or c i,1 with c′ i,1 , in a new work constellation where c′ i,0 and c′ i,1 are the next available levels smaller than c i,0 and c i,1 , respectively, in the set {L i,n ,n=u min . . . u max }. This replacement of the smallest or second-smallest level with a smaller level is illustrated in FIG. 2 .

Based on this consideration, one embodiment of the invention reduces the lower bound on minimum distance in accordance with the levels available in the sets {L i,n =u min . . . u max } as d min , LB = min 0 ≤ i ≤ 5  min  ( 2  c i , 0 ′ , c i , 1 ′ - c i , 0 ) EQ .    4

Because of some rare special cases, an additional step

d min,LB ←min( d min,LB ,d min,LB (0) −1)  EQ.5

is required to guarantee that the new lower bound d min,LB is smaller than d (0) min,LB . Note that other embodiments are possible for the operation of reducing the lower bound on minimum distance in lock step with the available levels.

Similarly, in cases where d min,LB needs to be increased, it is possible to replace the smallest or second-smallest level by the next larger level available in {L i,n ,n=u min . . . u max }, which leads to efficient rules for increasing d min,LB in lock step with the available levels.

Pruning of Work Constellations

The submethod for pruning eliminates ucodes and corresponding levels from a work constellation set until none of the moduli can be reduced without also reducing K=└log 2 (P)┘ (and hence the data rate), where P is the product of the moduli M i . Optionally, the power constraint P avg ≦P max can be enforced, which may reduce K. The pruning algorithm takes advantage of the fact that a modulus M i can be decreased by 1 without decreasing K if (M i −1)(P−Q)≧Q, where Q=2 K . This condition is easily checked with a 16×32 bit multiplication followed by a 48-bit comparison. The pruning method PM is defined as follows:

Step PM1: Among all intervals i satisfying (M,−1)(P−Q)≧Q, remove the largest level from the work constellation set, decrease the corresponding modulus M j , and update P. Repeat PM1 until (M i −1)(P−Q)≧Q is not satisfied for any i.

Description of Method for Constellation Generation

At the beginning of constellation generation, it is usually desirable to select a minimum spacing between levels, d min,LB , such that the set of work constellations obtained for d min,LB will give rise to a (non-zero) symbol error rate that is close to a desired operating point. (It is well known to those skilled in the art that for modem connections employing layer- 2 error correction by means of retransmission, the optimal operating point in terms of overall data throughput is typically in the range from 10 −6 to 10 −4 symbol errors per second.).

For uniformly spaced signal alphabets, as in traditional quadrature amplitude modulation (QAM) systems, the computation of a suitable d min,LB as a function of the desired symbol error probability, the MSE, and the power limit is straightforward and well-known to those skilled in the art (Cf. John G. Proakis, Digital Communications, 1995). For nonuniformly spaced signal alphabets as employed in PCM modems, however, the symbol error probability depends on a multitude of different spacings between signal levels, where each spacing typically occurs with a different multiplicity. Moreover, these spacings and multiplicities of spacings depend on the impairments encountered on a given modem connection. In order to approach the desired operating point as closely as possible and reduce the variability of the achieved symbol error rate, it is therefore important to calculate the expected symbol error probability based on the constructed set of work constellations. Note that this calculation involves two computationally expensive operations, namely generating the set of work constellations and computing the symbol error probability based on these work constellations.

A preferred embodiment of the constellation generation method described in the present invention is illustrated in FIG. 3 .

The input parameters for constellation generation are the MSE measured during startup, the power limit P max , the detected pad attenuation,.the target symbol error probability P e,T , and the range of ucodes considered for constellation generation, given by u min and u max . For data rate limiting in modem testing, one may also specify a maximum number of bits entering the modulus encoder, K max .

In the first step (block 100 ), the input parameters are processed. A conservative value of d min,LB is computed based on the MSE and P e,T . In other embodiments of this step, the initial value of d min,LB can be tabulated as a function of the MSE.

In the next step (block 110 ), the initial value of d min,LB is used to generate a set of work constellations for which the probability of symbol error P e is computed. Typically, the value of P e obtained after the first iteration in block 110 is considerably smaller than the target probability of error because the initial d min,LB was conservative. The value of d min,LB is iteratively reduced until the error probability slightly exceeds the target error probability. As a further modification, a d min,LB that is between the values computed in the last two iterations of this step can be used to approximate d min,LB more closely.

The next step (block 120 ) prunes the set of work constellations and computes average power until the power constraint is satisfied. In a preferred embodiment, the pruning iteratively removes the largest level across the six intervals until the removal of another largest level would result in a reduction of the current parameter K, at which point average power is computed and compared to the power limit. If average power exceed the power limit, K is decremented by 1 (reducing the data rate accordingly) and the above process is repeated. The last iteration in this step results in the constellation power being at or below the power limit.

The next step (block 130 ) is used for fine-tuning the set of work constellations to approach the power limit as closely as possible. In a preferred embodiment, this can be achieved by increasing d min,LB and, optionally, by reducing the multiplicities of signal levels which are at d min,LB with respect to a neighboring level. In practice, the number of iterations of this step can be limited by accepting a set of work constellations if the average power is within a margin (e.g., 0.25 dB) from the power limit.

In the preferred embodiment, a final step (block 140 ) can be used to enforce the power constraint using the exact distribution. Typically, this step does not lead to any changes in the constellation set but is added as a safety measure in case the exact distribution results in an average power exceeding the power limit while the uniform distribution did not. Note that, in all the previous steps, a close to uniform signal-point distribution is maintained, simplifying the computation of both error probability and power.

The present invention has been described herein with reference to flowchart and/or block diagram illustrations of methods, apparatus (systems), and computer program products according to an embodiment of the invention. It will be understood that each block of the flowchart and/or block diagram illustrations, and combinations of blocks in the flowchart and/or block diagram illustrations, may be implemented by computer program instructions. These computer program instructions may be provided to a processor of a general purpose computer, special purpose computer, or other programmable data processing apparatus to produce a machine, such that the instructions, which execute via the processor of the computer or other programmable data processing apparatus, create means for implementing the functions specified in the flowchart and/or block diagram block or blocks. These computer program instructions may also be stored in a computer-usable or computer-readable memory that can direct a computer or other programmable data processing apparatus to function in a particular manner, such that the instructions stored in the computer-usable or computer-readable memory produce an article of manufacture including instruction means that implement the function specified in the flowchart and/or block diagram block or blocks.

The computer program instructions may also be loaded onto a computer or other programmable data processing apparatus to cause a series of operational steps to be performed on the computer or other programmable apparatus to produce a computer implemented process such that the instructions that execute on the computer or other programmable apparatus provide steps for implementing the functions specified in the flowchart and/or block diagram block or blocks.

The flowchart of FIG. 3 illustrates the architecture, functionality, and operation of a possible implementation of the client modem receiver software. In this regard, each block represents a module, segment, or portion of code, which comprises one or more executable instructions for implementing the specified logical function(s). It should also be noted that in some alternative implementations, the functions noted in the blocks may occur out of the order noted in the figures. For example, two blocks shown in succession may in fact be executed substantially concurrently or the blocks may sometimes be executed in the reverse order, depending upon the functionality involved.

While the present invention has been illustrated and described in detail in the drawings and foregoing description, it is understood that the embodiments shown are merely exemplary. Moreover, it is understood that many variations and modifications can be made to the embodiments described herein above without substantially departing from the principles of the present invention. All such variations and modifications are intended to be included herein within the scope of the present invention, as set forth in the following claims.