Power conversion device

This application claims priority to China Patent Application No. 202010234598.6, filed on Mar. 30, 2020. The entire contents of the above-mentioned patent application are incorporated herein by reference for all purposes.

The present disclosure relates to a power conversion device. More particularly, the present disclosure relates to a power conversion device capable of counteracting the DC magnetic fluxes generated by the windings of inductors.

In conventional non-isolated step-down applications with large current, a multi-phase asymmetric buck circuit topology is used to improve the power conversion efficiency. Specifically, in each phase of the asymmetric buck circuit, the windings of plural inductors are wound around the side pillars of the same magnetic component. Accordingly, the AC magnetic fluxes on the middle pillar of the magnetic component can be counteracted with each other, thereby reducing the ripple of the output current. However, if the DC currents flowing through the plural inductors are unequal, the DC magnetic fluxes on the side pillars would be large, which makes the magnetic core easy to be saturated.

Therefore, there is a need of providing a power conversion device to obviate the drawbacks encountered from the prior arts.

It is an objective of the present disclosure to provide a power conversion device. In a plurality of power conversion circuits, the DC currents flowing through the corresponding inductors which are corresponding to each other are equal. The windings of these corresponding inductors are wound around the side pillars of the same magnetic component, thus the DC magnetic fluxes on the side pillars can be counteracted by each other without disposing an air gap on the side pillars. Consequently, the loss of the power conversion device is reduced, and the magnetic core is prevented from being saturated easily.

In accordance with an aspect of the present disclosure, there is provided a power conversion device. The power conversion device includes an input port, an output port, N power conversion circuits and M magnetic components, where N and M are positive integers greater than 1. The N power conversion circuits are electrically connected between the input and output ports in parallel. Each of the N power conversion circuits includes M inductors. DC currents flowing through the M inductors respectively are unequal. The M inductors include at least one corresponding inductor. In the N power conversion circuits, DC currents flowing through the corresponding inductors which are corresponding to each other are equal. Each of the M magnetic components includes a middle pillar, N side pillars and two substrates. The middle pillar and the N side pillars are located between the two substrates. The middle pillar has an air gap. In the N power conversion circuits, windings of N corresponding inductors which are corresponding to each other are wound around the N side pillars of one of the M magnetic components.

FIG. 1 is a schematic circuit diagram illustrating a power conversion device according to a first embodiment of the present disclosure;

FIG. 2A and FIG. 2B are schematic views showing the structure of a magnetic component in the first embodiment of the present disclosure;

FIG. 3A and FIG. 3B are schematic views showing the winding manner of inductors in the first embodiment of the present disclosure;

FIG. 4 is a schematic circuit diagram illustrating a power conversion device according to a second embodiment of the present disclosure; and

FIG. 5A and FIG. 5B are schematic views showing the structure of a magnetic component in the second embodiment of the present disclosure.

The present disclosure will now be described in more detail with reference to the accompanying drawings. It is to be noted that the following descriptions are presented herein for illustrative purposes only. It is not intended to be exhaustive or to be limited to the precise form disclosed.

FIG. 1 is a schematic circuit diagram illustrating a power conversion device 100 according to a first embodiment of the present disclosure. FIG. 2A and FIG. 2B are schematic views showing the structure of a magnetic component 120 in the first embodiment of the present disclosure. As shown in FIGS. 1, 2A, and 2B , the power conversion device 100 of the present disclosure includes an input port Vin, an output port Vo, N power conversion circuits 110 and M magnetic components 120 , where both N and M are positive integers greater than 1.

The N power conversion circuits 110 are connected to each other in parallel and are electrically connected between the input port Vin and the output port Vo. Each of the N power conversion circuits 110 includes M inductors, and the currents flowing through the M inductors respectively are unequal. The M inductors in one of the N power conversion circuits 110 can correspond to at least one inductor in another one of the N power conversion circuits 110 . In the N power conversion circuits 110 , the currents flowing through the corresponding inductors which are corresponding to each other are equal.

As shown in FIGS. 2A and 2B , each of the M magnetic components 120 includes a middle pillar 25 , N side pillars 21 , 22 (here, N=2), and two substrates 23 , 24 . The middle pillar 25 and the N side pillars 21 , 22 are located between the two substrates 23 , 24 . The middle pillar has an air gap 26 that makes the equivalent reluctance of the middle pillar larger. In the N power conversion circuits 110 , the windings of the N corresponding inductors which are corresponding to each other are wound around the N side pillars 21 , 22 of the same magnetic component with the same winding direction. Consequently, with regard to each of the N side pillars 21 , 22 of the magnetic component, the DC magnetic fluxes flowing therethrough are counteracted by each other. Moreover, the DC magnetic fluxes are superimposed on the middle pillar 25 , thereby preventing the magnetic core of the magnetic component from being saturated easily. Further, since the air gap 26 only exist on the middle pillar 25 , the inductance of the corresponding inductor can be increased, and the output current ripple and loss of the power conversion device 100 are reduced. In addition, in an embodiment, the voltage signals on the N corresponding inductors wound around the same magnetic component are out of phase with respect to each other in sequence by an angle between (360/N+30) degrees and (360/N+30) degrees. Therefore, the AC magnetic fluxes on the middle pillar 25 of the magnetic component can be counteracted by each other.

In order to control the switches of the power conversion circuit 110 , the power conversion device 100 further includes a controller 101 . The controller output N control signals that are configured to control the N power conversion circuits 110 respectively. The N control signals have the same duty ratio. The N control signals may be at the same phase. Alternatively, the N control signals may be output of phase with respect to each other in sequence by an angle between (360/N−30) degrees and (360/N+30) degrees.

In an embodiment, each power conversion circuit includes M power conversion units, and each of the M power conversion units includes an inductor, a first switch and a second switch serially connected to the first switch. The first switch of the first power conversion unit is connected to the input port Vin, and the first switch of other power conversion unit is connected to the first switch of the preceding power conversion unit in sequence. In an embodiment, the N control signals control the first switches of the first power conversion units of the N power conversion circuit respectively. In each power conversion circuit, the control signals of the M first switches of the M power conversion units have the same duty ratio and are 360/M degrees out of phase with respect to each other. Moreover, in each power conversion unit, the control signals of the first and second switches are complementary to each other.

In accordance with the first embodiment shown in FIG. 1 , FIG. 2A and FIG. 2B , the actual implementation with N equal to 2 and M equal to 2 is exemplified as follows.

In the first embodiment shown in FIG. 1 , the power conversion device 100 includes two power conversion circuits X 1 and X 2 . In this embodiment, the power conversion circuit X 1 is connected to the input capacitor Cin 1 in parallel, and the power conversion circuit X 2 is connected to the input capacitor Cin 2 in parallel, but not exclusively. In another embodiment, the power conversion circuits X 1 and X 2 may be connected to the same input capacitor in parallel. The output port Vo of the power conversion device 100 is formed by connecting the output capacitor Co to the output terminals of the power conversion circuits X 1 and X 2 in parallel. The power conversion circuit X 1 includes two power conversion units. The first power conversion unit includes a first switch M 11 , a second switch M 13 and an inductor L 11 , and the second power conversion unit includes a first switch M 12 , a second switch M 14 and an inductor L 12 . The power conversion circuit X 2 includes two power conversion units. The first power conversion unit of the power conversion circuit X 2 includes a first switch M 21 , a second switch M 23 and an inductor L 21 , and the second power conversion unit of the power conversion circuit X 2 includes a first switch M 22 , a second switch M 24 and an inductor L 22 .

The controller 101 outputs two control signals PWM 1 and PWM 2 to control the two power conversion circuits X 1 and X 2 , respectively. The control signals PWM 1 and PWM 2 have the same duty ratio. The control signals PWM 1 and PWM 2 may be at the same phase, or the control signals PWM 1 and PWM 2 may be out of phase with respect to each other in sequence by an angle between 150 degrees and 210 degrees. For example but not exclusively, the control signals PWM 1 and PWM 2 may be pulse width modulation signals. In the power conversion circuit X 1 , the first switch M 11 is controlled by the control signal PWM 1 , and the control signal of the first switch M 12 and the control signal PWM 1 have the same duty ratio and are 180 degrees out of phase with respect to each other. The control signal of the second switch M 13 is complementary to the control signal PWM 1 , and the control signal of the second switch M 14 is complementary to the control signal of the first switch M 12 . In the power conversion circuit X 2 , the first switch M 21 is controlled by the control signal PWM 2 , and the control signal of the first switch M 22 and the control signal PWM 2 have the same duty ratio and are 180 degrees out of phase with respect to each other. The control signal of the second switch M 23 is complementary to the control signal PWM 2 , and the control signal of the second switch M 24 is complementary to the control signal of the first switch M 22 .

In the two power conversion circuits X 1 and X 2 , when the duty ratio of the two control signals PWM 1 and PWM 2 are greater than 50%, the DC currents flowing through the inductors L 11 and L 12 respectively are unequal, and the DC currents flowing through the inductors L 21 and L 22 respectively are unequal. The two inductors L 11 and L 12 of the power conversion circuit X 1 are a first corresponding inductor and a second corresponding inductor respectively. The two inductors L 21 and L 22 of the power conversion circuit X 2 are a first corresponding inductor and a second corresponding inductor respectively. The DC currents flowing through the two first corresponding inductors (i.e., the inductors L 11 and L 21 ), which are corresponding to each other, are equal. The DC currents flowing through the two second corresponding inductors (i.e., the inductors L 12 and L 22 ), which are corresponding to each other, are equal. It is noted that the description about the DC currents being equal or unequal means that the DC currents are substantially equal or unequal. For example, the DC currents are equal if the difference ratio therebetween is less than or equal to 20%, and the DC currents are unequal if the difference ratio therebetween is greater than 20%. The following description about the DC currents being equal or unequal means the same. In addition, the windings of the two first corresponding inductors (i.e., the inductors L 11 and L 21 ) are wound around the magnetic component 2 a of FIG. 2A , and the winding directions of the inductors L 11 and L 21 are the same. The windings of the two second corresponding inductors (i.e., the inductors L 12 and L 22 ) are wound around the magnetic component 2 b of FIG. 2B , and the winding directions of the inductors L 12 and L 22 are the same. However, the actual winding directions of the inductors are not limited to that shown in the drawings.

As shown in FIG. 2A , the magnetic component 2 a includes two side pillars 21 and 22 , two substrates 23 and 24 and a middle pillar 25 . The middle pillar 25 and the side pillars 21 and 22 are located between the two substrates 23 and 24 . The middle pillar 25 has an air gap 26 . In this embodiment, side pillars 21 , 22 and middle pillar 25 have a rectangular rail or bar shape. The winding of the inductor L 11 is wound around the side pillar 21 , and the winding of the inductor L 21 is wound around the side pillar 22 . The winding directions of the inductors L 11 and L 21 are the same, but not limited to that shown in the drawings. The DC magnetic flux generated by the inductor L 11 on the side pillar 21 is represented by Φ 11 . The DC magnetic flux Φ 11 may flow toward the side pillar 22 and the middle pillar 25 . The part of the DC magnetic flux Φ 11 flowing toward the side pillar 22 is represented by Φ( 11 - 1 ), and the part of the DC magnetic flux Φ 11 flowing toward the middle pillar 25 is represented by Φ( 11 - 2 ). The DC magnetic flux generated by the inductor L 21 on the side pillar 22 is represented by Φ 21 . The DC magnetic flux Φ 21 may flow toward the side pillar 21 and the middle pillar 25 . The part of the DC magnetic flux Φ 21 flowing toward the side pillar 21 is represented by Φ( 21 - 1 ), and the part of the DC magnetic flux Φ 21 flowing toward the middle pillar 25 is represented by Φ( 21 - 2 ). Since the middle pillar 25 has an air gap 26 , the equivalent reluctance of the middle pillar 25 is large, which causes the DC magnetic flux flowing toward the middle pillar 25 to be smaller.

According to Ohm's law for magnetic circuits, Φ 11 =Nt*I 11 /Rm 1 , and Φ( 21 - 1 )=Nt*I 21 /Rm 1 . Nt is the winding turns of the inductors L 11 and L 21 (as an example, the inductors L 11 and L 21 have the same winding turns). I 11 is the DC current flowing through the inductor L 11 . I 21 is the DC current flowing through the inductor L 21 . Rm 1 is the equivalent reluctance of the side pillars 21 and 22 (as an example, the side pillars 21 and 22 have the same equivalent reluctance). Therefore, the DC magnetic flux on the side pillar 21 equals Φ 11 −Φ( 21 - 1 )=Nt*(I 11 −I 21 )/Rm 1 . Since the DC currents flowing through the inductors L 11 and L 21 are equal, i.e., I 11 =I 21 , Φ 11 is equal to Φ( 21 - 1 ), the DC magnetic fluxes on the side pillar 21 are therefore counteracted by each other. Consequently, it is allowed to employ small reluctance Rm 1 , namely, there is no need to form air gap on the side pillar 21 , which can increase the inductance of the inductor L 11 and reduces the output current ripple and loss of the power conversion device 100 .

It is noted that the counteraction of the magnetic flux does not mean that the magnetic flux is zero. For example, there may be a residual magnetic flux after counteracting magnetic flux, and the amount of the residual magnetic flux is determined by the difference between the currents flowing through the corresponding inductors. The flowing description about the counteraction of magnetic flux means the same.

Similar to the magnetic fluxes on the side pillar 21 , the magnetic fluxes on the side pillar 22 are counteracted by each other without forming air gap on the side pillar 22 . Therefore, the inductance of the inductor L 21 can be increased, and the output current ripple and loss of the power conversion device 100 can be reduced. Also, the DC magnetic fluxes on the substrates are counteracted by each other. Consequently, the thickness of the substrates 23 and 24 can be decreased. As a result, the size of the magnetic component 2 a can be reduced.

In an embodiment, through the control signals PWM 1 and PWM 2 being out of phase with respect to each other, the voltage signals on the inductors L 11 and L 21 may be out of phase with respect to each other by an angle between 150 degrees and 210 degrees (for example but not limited to 180 degrees). Consequently, the AC magnetic fluxes on the middle pillar 25 of the magnetic component 2 a are counteracted by each other, which can increase the equivalent inductances of the inductors L 11 and L 21 and reduce the ripple of the output current.

For the same reason, in FIG. 2B , the windings of the inductors L 12 and L 22 are wound around the side pillars 21 and 22 of the magnetic component 2 b respectively. The counteraction of DC magnetic flux is achieved on the side pillars 21 and 22 of the magnetic component 2 b . The elements of the magnetic component 2 b which are similar to that of the magnetic component 2 a are designated by identical numeral references, the counteraction principle for the magnetic component 2 b is the same as that for the magnetic component 2 a , and thus the detailed descriptions thereof are omitted herein. In an embodiment, through the control signals PWM 1 and PWM 2 being out of phase with respect to each other, the voltage signals on the inductors L 12 and L 22 may be out of phase with respect to each other by an angle between 150 degrees and 210 degrees (for example but not limited to 180 degrees). Consequently, the AC magnetic fluxes on the middle pillar 25 of the magnetic component 2 b are counteracted by each other, which can increase the equivalent inductances of the inductors L 12 and L 22 and reduce the ripple of the output current.

FIG. 3A illustrates a winding manner of the inductors L 11 and L 21 in accordance with an embodiment of the present disclosure. FIG. 3B illustrates the winding manner of the inductors L 12 and L 22 in accordance with an embodiment of the present disclosure. As shown in FIGS. 3A and 3B , the preconditions are winding the windings of the corresponding inductors (e.g., L 12 and L 22 ) on different side pillars of the same magnetic component, thereby allowing the DC magnetic fluxes on the side pillars to be counteracted by each other without forming air gap on the side pillar. It is to be appreciated that, so long as the preconditions are satisfied, the winding position of the inductors, the entire structure of the magnetic components 2 a and 2 b and the shape and size of the side and middle pillars of the magnetic components 2 a and 2 b can be adjusted according to actual requirements without being limited to the exemplified manner as shown in the drawings.

For example but not exclusively, the magnetic component ( 2 a , 2 b ) can be formed by two magnetic cores assembled together. In an embodiment, one magnetic core may have a first substrate, the middle pillar 25 and the side pillars 21 and 22 formed on the first substrate, while the other magnetic core may have a second substrate without any pillars. In another embodiment, one magnetic core may have a first substrate, a part of the middle pillar 25 and a part of the side pillars 21 and 22 formed on the first substrate, while the other magnetic core may have a second substrate, the other part of the middle pillar 25 and the other part of the side pillars 21 and 22 formed on the second substrate.

FIG. 4 is a schematic circuit diagram illustrating a power conversion device 200 according to a second embodiment of the present disclosure. FIG. 5A and FIG. 5B are schematic views showing the structure of a magnetic component in the second embodiment of the present disclosure. In accordance with the second embodiment shown in FIG. 4 , FIG. 5A and FIG. 5B , the actual implementation with N equal to 4 and M equal to 2 is exemplified as follows. Compared with the first embodiment, the second embodiment can further increase the load capacity of the power conversion device.

In the second embodiment shown in FIG. 4 , the power conversion device 200 includes four power conversion circuits X 1 , X 2 , X 3 and X 4 . In this embodiment, the power conversion circuit X 1 is connected to the input capacitor Cin 1 in parallel; the power conversion circuit X 2 is connected to the input capacitor Cin 2 in parallel; the power conversion circuit X 3 is connected to the input capacitor Cin 3 in parallel; and the power conversion circuit X 4 is connected to the input capacitor Cin 4 in parallel, but not exclusively. In another embodiment, the power conversion circuits X 1 , X 2 , X 3 and X 4 may be connected to the same input capacitor in parallel. The output port Vo of the power conversion device 200 is formed by connecting the output capacitor Co to the output terminals of the power conversion circuits X 1 , X 2 , X 3 and X 4 in parallel.

The components of the power conversion circuits X 1 and X 2 in the second embodiment are the same as that in the first embodiment, thus the detailed descriptions thereof are omitted herein. The power conversion circuit X 3 includes two power conversion units. The first power conversion unit of the power conversion circuit X 3 includes a first switch M 31 , a second switch M 33 and an inductor L 31 . The second power conversion unit of the power conversion circuit X 3 includes a first switch M 32 , a second switch M 34 and an inductor L 32 . The power conversion circuit X 4 includes two power conversion units. The first power conversion unit of the power conversion circuit X 4 includes a first switch M 41 , a second switch M 43 and an inductor L 41 . The second power conversion unit of the power conversion circuit X 4 includes a first switch M 42 , a second switch M 44 and an inductor L 42 .

The controller 201 output four control signals PWM 1 , PWM 2 , PWM 3 and PWM 4 to control the four power conversion circuits X 1 , X 2 , X 3 and X 4 respectively. The control signals PWM 1 , PWM 2 , PWM 3 and PWM 4 have the same duty ratio. The control signals PWM 1 , PWM 2 , PWM 3 and PWM 4 may be at the same phase, or the control signals PWM 1 , PWM 2 , PWM 3 and PWM 4 may be out of phase with respect to each other in sequence by an angle between 60 degrees and 120 degrees. For example but not exclusively, the control signals PWM 1 , PWM 2 , PWM 3 and PWM 4 are pulse width modulation signals.

The control manner for the power conversion circuits X 1 and X 2 in the second embodiment is the same as that in the first embodiment, and the detailed descriptions thereof are omitted herein. In the power conversion circuit X 3 , the first switch M 31 is controlled by the control signal PWM 3 , and the control signal of the first switch M 32 and the control signal PWM 3 have the same duty ratio and are 180 degrees out of phase with respect to each other. The control signal of the second switch M 33 is complementary to the control signal PWM 3 , and the control signal of the second switch M 34 is complementary to the control signal of the first switch M 32 . In the power conversion circuit X 4 , the first switch M 41 is controlled by the control signal PWM 4 , and the control signal of the first switch M 42 and the control signal PWM 4 have the same duty ratio and are 180 degrees out of phase with respect to each other. The control signal of the second switch M 43 is complementary to the control signal PWM 4 , and the control signal of the second switch M 44 is complementary to the control signal of the first switch M 42 .

In the four power conversion circuits X 1 , X 2 , X 3 and X 4 , when the duty ratio of the four control signals PWM 1 , PWM 2 , PWM 3 and PWM 4 are greater than 50%, the DC currents flowing through the inductors L 11 and L 12 respectively are unequal, the DC currents flowing through the inductors L 21 and L 22 respectively are unequal, the DC currents flowing through the inductors L 31 and L 32 respectively are unequal, and the DC currents flowing through the inductors L 41 and L 42 respectively are unequal. The two inductors L 11 and L 12 of the power conversion circuit X 1 are a first corresponding inductor and a second corresponding inductor respectively. The two inductors L 21 and L 22 of the power conversion circuit X 2 are a first corresponding inductor and a second corresponding inductor respectively. The two inductors L 31 and L 32 of the power conversion circuit X 3 are a first corresponding inductor and a second corresponding inductor respectively. The two inductors L 41 and L 42 of the power conversion circuit X 4 are a first corresponding inductor and a second corresponding inductor respectively.

The DC currents flowing through the four first corresponding inductors (i.e., the inductors L 11 , L 21 , L 31 and L 41 ), which are corresponding to each other, are equal. The DC currents flowing through the four second corresponding inductors (i.e., the inductors L 12 , L 22 , L 32 and L 42 ), which are corresponding to each other, are equal. In addition, the windings of the four first corresponding inductors (i.e., the inductors L 11 , L 21 , L 31 and L 41 ), which are corresponding to each other, are wound around the magnetic component 3 a of FIG. 5A , and the winding directions of the inductors L 11 , L 21 , L 31 and L 41 are the same (e.g., counterclockwise). The windings of the four second corresponding inductors (i.e., the inductors L 12 , L 22 , L 32 and L 42 ), which are corresponding to each other, are wound around the magnetic component 3 b of FIG. 5B , and the winding directions of the inductors L 12 , L 22 , L 32 and L 42 are the same (e.g., counterclockwise). However, the actual winding directions of the inductors are not limited to that shown in the drawings.

FIG. 5A and FIG. 5B show the partial structures of the magnetic components 3 a and 3 b respectively.

As shown in FIG. 5A , the magnetic component 3 a includes a middle pillar 30 , four side pillars 31 , 32 , 33 and 34 , and two substrates (only one substrate 35 is shown in FIG. 5A ). The middle pillar 30 and the four side pillars 31 , 32 , 33 and 34 are located between the two substrates. In this embodiment, the middle pillar 30 and side pillars 31 , 32 , 33 , 34 have a cylindrical shape. It is appreciated that middle pillar 30 and side pillars 31 , 32 , 33 , 34 can have any other suitable shapes, such as, a triangular prism shape, a rectangular prism shape, a hexagonal prism shape, etc. The four side pillars 31 , 32 , 33 and 34 are disposed around the middle pillar 30 . The middle pillar 30 has an air gap (not shown). The windings of the inductor L 11 , L 21 , L 31 and L 41 are wound around the side pillars 31 , 32 , 33 and 34 . The winding directions of the inductors L 11 , L 21 , L 31 and L 41 are the same (e.g., counterclockwise), but not limited to that shown in the drawings. Accordingly, the counteraction of DC magnetic flux is achieved on the four side pillars 31 , 32 , 33 and 34 , the counteraction principle can be derived from the first embodiment, and the detailed descriptions thereof are thus omitted herein.

In an embodiment, through the control signals PWM 1 , PWM 2 , PWM 3 and PWM 4 being out of phase with respect to each other, the voltage signals on the inductors L 11 , L 21 , L 31 and L 41 may be out of phase with respect to each other by an angle between 60 degrees and 120 degrees (for example but not limited to 90 degrees). Consequently, the AC magnetic fluxes on the middle pillar 30 are counteracted by each other, which can increase the equivalent inductances of the inductors L 11 , L 21 , L 31 and L 41 and reduce the ripple of the output current.

For the same reason, in FIG. 5B , the windings of the inductors L 12 , L 22 , L 32 and L 42 are wound around the side pillars 31 , 32 , 33 and 34 of the magnetic component 3 b with the same winding direction (e.g., counterclockwise). The counteraction of DC magnetic flux is achieved on the side pillars 31 , 32 , 33 and 34 of the magnetic component 3 b . The elements of the magnetic component 3 b which are similar to that of the magnetic component 3 a are designated by identical numeral references, the counteraction principle for the magnetic component 3 b is the same as that for the magnetic component 3 a , and thus the detailed descriptions thereof are omitted herein. In an embodiment, through the control signals PWM 1 , PWM 2 , PWM 3 and PWM 4 being out of phase with respect to each other, the voltage signals on the inductors L 12 , L 22 , L 32 and L 42 may be out of phase with respect to each other by an angle between 60 degrees and 120 degrees (for example but not limited to 90 degrees). Consequently, the AC magnetic fluxes on the middle pillar 30 are counteracted by each other, which can increase the equivalent inductances of the inductors L 12 , L 22 , L 32 and L 42 and reduce the ripple of the output current.

From the above descriptions, the present disclosure provides a power conversion device. In a plurality of power conversion circuits, the DC currents respectively flowing through the corresponding inductors are equal. The windings of these corresponding inductors are wound around the side pillars of the same magnetic component, thus the DC magnetic fluxes on the side pillars can be counteracted by each other without forming an air gap on the side pillars. Consequently, the loss of the power conversion device is reduced, and the magnetic core is prevented from being saturated easily. Moreover, the DC magnetic fluxes on the substrates are counteracted by each other. Therefore, the thickness of the substrates can be decreased, and the size of the magnetic component can be reduced.

While the present disclosure has been described in terms of what is presently considered to be the most practical and preferred embodiments, it is to be understood that the claimed scope of the present disclosure needs not be limited to the disclosed embodiments.