Power supply device and lighting apparatus using the same

This application claims the benefit of priority of Japanese Patent Application Number 2014-39148, filed on Feb. 28, 2014, the entire contents of which are hereby incorporated by reference.

This invention generally relates to power supply devices and lighting apparatuses using the same, and more specifically relates to a power supply device configured to supply electric power to a load and a lighting apparatus using the same.

Heretofore, switching power supply circuits that are included in various electronic apparatuses as a power supply have been proposed (refer to JP 2001-339948 A, hereinafter referred to as “Document 1”, for example).

A switching power supply circuit described in Document 1 includes a full-wave rectifying circuit including a bridge rectifying circuit and a smoothing capacitor, and a main switching element. Also, the switching power supply circuit includes a switching driving unit configured to drive the main switching element, and an insulated converter transformer that includes a primary winding and a secondary winding.

A MOSFET (Metal Oxide Semiconductor Field Effect Transistor) is used as the main switching element. A parallel resonance capacitor is connected between a drain and a source of the main switching element. Also, a clamp diode is connected between the drain and source of the main switching element.

An active clamp circuit is connected in parallel to the primary winding. The active clamp circuit includes an auxiliary switching element, a self-excited driving circuit configured to drive the auxiliary switching element, a clamp capacitor, and a clamp diode. The self-excited driving circuit includes a drive winding that is provided in the insulated converter transformer, a capacitor, and two resistors.

A voltage doubler half-wave rectifying circuit is formed on a secondary side of the insulated converter transformer. The voltage doubler half-wave rectifying circuit includes a secondary winding, a serial resonance capacitor, a first rectifying diode, a second rectifying diode, and a smoothing capacitor. The serial resonance capacitor is connected in series to the secondary winding. The first rectifying diode is connected in parallel to a series circuit of the secondary winding and the serial resonance capacitor. A series circuit of the second rectifying diode and the smoothing capacitor is connected in parallel to the series circuit of the secondary winding and the serial resonance capacitor.

As described above, since the voltage doubler half-wave rectifying circuit is formed on the secondary side of the insulated converter transformer in the conventional switching power supply circuit described in Document 1, it is difficult to further downsize the switching power supply circuit. Also, it is desired recently that power supply devices that are included in various electronic apparatuses as a power supply is further downsized.

The present invention has been made in view of the above-described problems, and an object of the present invention is to provide a power supply device that is capable of being further downsized, and a lighting apparatus that uses the power supply device.

A power supply device according to an aspect of the present invention includes: a power supply unit configured to generate a first DC voltage from an input voltage; a conversion unit configured to convert the first DC voltage outputted from the power supply unit to a second DC voltage that is different from the first DC voltage; and a control unit configured to control the conversion unit. The conversion unit is an active clamp type flyback converter. The conversion includes: a main switching element; a sub switching element; a flyback transformer including a primary winding and a secondary winding; and a rectifying element configured to perform half-wave rectification on a first voltage generated in the secondary winding. The main switching element and the sub switching element each include a first main terminal, a second main terminal, and a control terminal. The primary winding is connected in series to the main switching element, and is connected in parallel to a series circuit of a resonance capacitor and the sub switching element. The secondary winding is connected in series to a series circuit of the rectifying element and a resonance inductor. The control unit is configured to control the main switching element and the sub switching element. The control unit includes, as control modes, a first control mode in which the main switching element is put in an on state and the sub switching element is put in an off state, a second control mode in which the main switching element is put in an off state and the sub switching element is put in an on state, and a third control mode in which the main switching element and the sub switching element are both put in off states. The control unit is configured to alternate between the first control mode and the second control mode via the third control mode. A capacitance of the resonance capacitor and an inductance of the resonance inductor are each set such that, in a period in which the main switching element is in an off state and the sub switching element is in an on state, a waveform, with respect to time in the period, of a second voltage that is generated between the first main terminal and the second main terminal of the main switching element takes a protruding curve shape, the voltage being generated due to a resonance phenomenon of at least the resonance capacitor, the primary winding, and the resonance inductor.

A lighting apparatus according to another aspect of the present invention includes the above-described power supply device; a light source unit that can be operated by the power supply device, and an apparatus body to which the power supply device and the light source unit are attached.

The figures depict one or more implementations in accordance with the present teaching, by way of example only, not by way of limitations. In the figures, like reference numerals refer to the same or similar elements.

FIG. 1 is a circuit diagram of a power supply device according to Embodiment 1;

FIG. 2 is a timing chart illustrating operations of the power supply device according to Embodiment 1;

FIG. 3 is a circuit diagram of a simulation model of the power supply device according to Embodiment 1;

FIG. 4 is a timing chart, which is a result of simulation performed using the simulation model, illustrating operations of the power supply device;

FIG. 5 is another timing chart, which is a result of simulation performed using the simulation model, illustrating operations of the power supply device;

FIG. 6 is yet another timing chart, which is a result of simulation performed using the simulation model, illustrating operations of the power supply device;

FIG. 7 is a correlation diagram between a winding ratio of a transformer and capacitance of a resonance capacitor with respect to a result of simulation performed using the simulation model of the power supply device;

FIG. 8 is a schematic side view of a lighting apparatus according to Embodiment 1 in an installed state;

FIG. 9 is a schematic perspective view of the lighting apparatus according to Embodiment 1;

FIG. 10 is a circuit diagram of a power supply device according to Embodiment 2;

FIG. 11 is a circuit diagram illustrating a rectifying circuit, a power factor improving circuit, and a power supply unit in the power supply device according to Embodiment 2; and

FIG. 12 is a circuit diagram of a power supply device serving as a comparative example.

Hereinafter, a power supply device 10 according to the present embodiment will be described with reference to FIGS. 1 and 2 .

The power supply device 10 is configured to supply electric power to a load 21 . A light source unit 23 including two or more solid-state light emitting elements 22 or the like can be used as the load 21 , for example. A light emitting diode or the like can be used as the solid-state light emitting element 22 , for example. Note that the power supply device 10 does not include the load 21 as a constituent element.

The light source unit 23 includes the two or more solid-state light emitting elements 22 . Although the electrical connection of the solid-state light emitting elements 22 is a serial connection, the electrical connection is not limited to a serial connection. The electrical connection of the solid-state light emitting elements 22 may be a parallel connection, or may be a connection in which a serial connection and a parallel connection are combined. The emitting light color of the solid-state light emitting element 22 is assumed to be white, but the emitting light color is not limited to white.

Although the number of the solid-state light emitting elements 22 is two or more in the light source unit 23 , the number may be one. A light emitting diode is used as the solid-state light emitting element 22 in the light source unit 23 , but the light emitting element is not limited to the light emitting diode. A semiconductor laser element, an organic electroluminescent element, or the like may be used as the solid-state light emitting element 22 in the light source unit 23 , for example. Note that, although the light source unit 23 is used as the load 21 in the power supply device 10 , the load is not limited to the light source unit 23 . A secondary battery or the like may be used as the load 21 in the power supply device 10 , for example.

The power supply device 10 includes a power supply unit 1 configured to generate a DC voltage (a first DC voltage) from an input voltage, a conversion unit 2 configured to convert the first DC voltage outputted from the power supply unit 1 to a DC voltage (a second DC voltage) that is different from the first DC voltage, and a control unit 3 configured to control the conversion unit 2 .

A phase control circuit 11 configured to perform phase-control on a sine wave-like AC voltage is electrically connected to an input side of the power supply unit 1 . A commercial power supply 25 or the like is electrically connected to an input side of the phase control circuit 11 , for example. The phase control circuit 11 is configured to perform light modulation of each of the solid-state light emitting elements 22 in the light source unit 23 that is electrically connected to an output side of the conversion unit 2 . A light modulator or the like can be used as the phase control circuit 11 , for example.

The power supply unit 1 is configured to acquire a voltage that is phase-controlled by the phase control circuit 11 as the input voltage, and generate the first DC voltage from the input voltage. A rectifying and smoothing circuit that includes a diode bridge and a capacitor, or the like, can be used as the power supply unit 1 , for example.

The conversion unit 2 is an active clamp type flyback converter. The conversion unit 2 includes a main switching element Q 1 , a sub switching element Q 2 , a flyback transformer T 1 , and a rectifying element 4 . The main switching element Q 1 and the sub switching element Q 2 each have a transistor structure. A normally off type n-channel MOSFET (Metal Oxide Semiconductor Field Effect Transistor) or the like can be used as the main switching element Q 1 and the sub switching element Q 2 , for example. The flyback transformer T 1 includes a primary winding L 1 and a secondary winding L 2 . The rectifying element 4 is configured to perform half-wave rectification on a voltage generated in the winding L 2 . A diode (first diode) or the like can be used as the rectifying element 4 , for example. A tertiary winding L 3 and a quaternary winding L 4 are provided on a primary side of the transformer T 1 . The tertiary winding L 3 and the quaternary winding L 4 are magnetically coupled to the primary winding L 1 . Specifically, the quaternary winding L 4 is magnetically coupled to the primary winding L 1 such that a voltage having a polarity opposite to that of the voltage generated in the primary winding L 1 can be obtained.

A first end of the primary winding L 1 is connected to a high potential side of the power supply unit 1 , and is connected to a first main terminal (drain terminal, in the present embodiment) of the sub switching element Q 2 via a resonance capacitor C 1 . A second main terminal (source terminal, in the present embodiment) of the sub switching element Q 2 is connected to a second end of the primary winding L 1 , and is connected to a first main terminal (drain terminal, in the present embodiment) of the main switching element Q 1 . In short, the primary winding L 1 is connected in series to the main switching element Q 1 , and is connected in parallel to a series circuit of the resonance capacitor C 1 and the sub switching element Q 2 .

A second main terminal (source terminal, in the present embodiment) of the main switching element Q 1 is connected to a low potential side of the power supply unit 1 via a resistor R 1 . The low potential side of the power supply unit 1 is grounded.

Control terminals (gate terminals, in the present embodiment) of the main switching element Q 1 and the sub switching element Q 2 are connected to the control unit 3 . A diode 7 in FIG. 1 represents a parasitic diode of an n-channel MOSFET used as the main switching element Q 1 . Also, a capacitor 8 in FIG. 1 represents a parasitic capacitor of the n-channel MOSFET used as the main switching element Q 1 . A diode 9 in FIG. 1 represents a parasitic diode of an n-channel MOSFET used as the sub switching element Q 2 .

A first end of the secondary winding L 2 is connected to a first end of the rectifying element 4 (anode of a diode, in the present embodiment). A second end of the rectifying element 4 (cathode of the diode, in the present embodiment) is connected to a first end of a resonance inductor L 5 . A second end of the resonance inductor L 5 is connected to a high potential side of a capacitor C 2 for smoothing. A low potential side of the capacitor C 2 is connected to a second end of the secondary winding L 2 . The second end of the secondary winding L 2 is connected to the low potential side of the power supply unit 1 . In short, the secondary winding L 2 is connected in series to a series circuit of the rectifying element 4 and the resonance inductor L 5 .

The control unit 3 is configured to control the main switching element Q 1 and the sub switching element Q 2 . Also, the control unit 3 includes, as control modes, a first control mode, a second control mode, a third control mode. The first control mode is a control mode in which the main switching element Q 1 is put in an on state, and the sub switching element Q 2 is put in an off state. The second control mode is a control mode in which the main switching element Q 1 is put in an off state, and the sub switching element Q 2 is put in an on state. The third control mode is a control mode in which the main switching element Q 1 and the sub switching element Q 2 are both put in off states. The control unit 3 is configured to alternate between the first control mode and the second control mode via the third control mode, as shown in FIG. 2 . Note that S 1 in FIG. 2 represents a period in which the control mode of the control unit 3 is the first control mode. Also, S 2 in FIG. 2 represents a period in which the control mode of the control unit 3 is the second control mode. Also, S 3 in FIG. 2 represents a period in which the control mode of the control unit 3 is the third control mode.

The control unit 3 includes a first control circuit 5 and a second control circuit 6 . The first control circuit 5 is configured to control the main switching element Q 1 . The second control circuit 6 is configured to control the sub switching element Q 2 .

The first control circuit 5 is configured to control the main switching element Q 1 based on the magnitude of an output current I 1 of the conversion unit 2 . The operation power supply of the first control circuit 5 is a voltage generated in the tertiary winding L 3 of the transformer T 1 . A first end of the tertiary winding L 3 is connected to an anode of a diode D 1 . A cathode of the diode D 1 is connected to the first control circuit 5 . Also, the cathode of the diode D 1 is connected to the low potential side of the power supply unit 1 via a capacitor C 3 . A second end of the tertiary winding L 3 is connected to an anode of a diode D 2 via a resistor R 2 . The anode of the diode D 2 is connected to the first control circuit 5 . A cathode of the diode D 2 is connected to the low potential side of the power supply unit 1 . Since the tertiary winding L 3 is magnetically coupled to the primary winding L 1 in the power supply device 10 , current flows in the tertiary winding L 3 when current flows in the primary winding L 1 . Accordingly, the first control circuit 5 can use voltage generated in the tertiary winding L 3 of the transformer T 1 as an operation power supply.

The first control circuit 5 is configured to receive a first detection signal corresponding to the output current I 1 of the conversion unit 2 . The first control circuit 5 is connected to the low potential side of the capacitor C 2 via a series circuit of a resistor R 5 and a resistor R 6 . The light source unit 23 is connected between a connection point of the resistor R 5 and resistor R 6 and the high potential side of the capacitor C 2 in the power supply device 10 . An anode side of the light source unit 23 is connected to the high potential side of the capacitor C 2 . A cathode side of the light source unit 23 is connected to the connection point of the resistor R 5 and the resistor R 6 .

The resistor R 5 is a resistor for detecting the output current I 1 of the conversion unit 2 . That is to say, in the power supply device 10 , the magnitude of a voltage across the resistor R 5 corresponds to the magnitude of the output current I 1 of the conversion unit 2 . That is, the larger the output current I 1 is, the larger the voltage across the resistor R 5 is. In the power supply device 10 , a voltage signal of the voltage across the resistor R 5 constitutes the first detection signal for detecting the output current I 1 of the conversion unit 2 . That is to say, the magnitude of the first detection signal corresponds to the magnitude of the voltage across the resistor R 5 . The larger the voltage across the resistor R 5 is, the larger the first detection signal is. Accordingly, the first control circuit 5 can detect the output current I 1 of the conversion unit 2 , and can control the main switching element Q 1 based on the magnitude of the first detection signal. In other words, the first control circuit 5 is configured to control the main switching element Q 1 based on the magnitude of the output current I 1 of the conversion unit 2 . Accordingly, the first control circuit 5 can make the output current I 1 of the conversion unit 2 constant. That is, the control unit 3 controls the conversion unit 2 such that the output current I 1 of the conversion unit 2 is constant.

Also, the first control circuit 5 is configured to receive a second detection signal that corresponds to a current I 2 flowing in the main switching element Q 1 . The first control circuit 5 is connected to a source terminal of the main switching element Q 1 .

The resistor R 1 is a resistor for detecting the current I 2 flowing in the main switching element Q 1 . That is to say, in the power supply device 10 , the magnitude of a voltage across the resistor R 1 corresponds to the magnitude of the current I 2 flowing in the main switching element Q 1 . That is, the larger the current I 2 is, the larger the voltage across the resistor R 1 is. In the power supply device 10 , a voltage signal of the voltage across the resistor R 1 constitutes the second detection signal for detecting the current I 2 flowing in the main switching element Q 1 . That is, the magnitude of the second detection signal corresponds to the magnitude of the voltage across the resistor R 1 . The larger the voltage across the resistor R 1 is, the larger the second detection signal is. Accordingly, the first control circuit 5 can detect the current I 2 flowing in the main switching element Q 1 , and can control the main switching element Q 1 based on the magnitude of the second detection signal.

The first control circuit 5 is configured to receive a power supply information signal that includes power supply information. The power supply information includes at least one of a waveform of the input voltage of the power supply unit 1 , an amplitude in the input voltage of the power supply unit 1 , and a phase in the input voltage of the power supply unit 1 . The first control circuit 5 is connected to a connection point of the phase control circuit 11 and the power supply unit 1 . In the power supply device 10 , the power supply information signal is a light modulation signal (first light modulation signal) for instructing a light modulation level of the solid-state light emitting elements 22 , for example, and has a waveform of a voltage on which phase control is performed by the phase control circuit 11 . Accordingly, the power supply device 10 can perform light modulation of the light source unit 23 based on the power supply information (phase, in the present embodiment) of the power supply information signal, for example.

Also, the first control circuit 5 is configured to receive a third detection signal that corresponds to the output voltage V 1 of the conversion unit 2 . A series circuit of a resistor R 7 and a resistor R 8 is connected in parallel to the capacitor C 2 . The first control circuit 5 is connected to a connection point of the resistor R 7 and the resistor R 8 .

The series circuit of the resistor R 7 and the resistor R 8 is a voltage-dividing circuit for detecting the output voltage V 1 of the conversion unit 2 . That is to say, in the power supply device 10 , the magnitude of a voltage across the resistor R 8 corresponds to the magnitude of the output voltage V 1 of the conversion unit 2 . That is, the larger the output voltage V 1 is, the larger the voltage across the resistor R 8 is. In the power supply device 10 , a voltage signal of the voltage across the resistor R 8 constitutes the third detection signal for detecting the output voltage V 1 of the conversion unit 2 . That is, the magnitude of the third detection signal corresponds to the magnitude of the voltage across the resistor R 8 . The larger the voltage across the resistor R 8 is, the larger the third detection signal is. Accordingly, the first control circuit 5 can detect the output voltage V 1 of the conversion unit 2 , and can control the main switching element Q 1 based on the magnitude of the third detection signal. That is, the first control circuit 5 is configured to control the main switching element Q 1 based on the magnitude of the third detection signal.

The second control circuit 6 is a self-excited type control circuit. The second control circuit 6 is configured to control the sub switching element Q 2 based on the magnitude of a voltage generated in the quaternary winding L 4 . The second control circuit 6 includes two resistors R 3 and R 4 and a capacitor C 4 . A first end of the quaternary winding L 4 is connected to the drain terminal of the main switching element Q 1 and the source terminal of the sub switching element Q 2 . A second end of the quaternary winding L 4 is connected to the drain terminal of the main switching element Q 1 and the source terminal of the sub switching element Q 2 via a series circuit of the resistor R 3 , the capacitor C 4 , and the resistor R 4 . The connection point of the capacitor C 4 and the resistor R 4 is connected to the gate terminal of the sub switching element Q 2 . Accordingly, it becomes possible for the second control circuit 6 to turn on and off the sub switching element Q 2 in coordination with the turning on and off of the main switching element Q 1 by the first control circuit 5 . That is to say, the second control circuit 6 is configured to turn on and off the sub switching element Q 2 in coordination with the turning on and off of the main switching element Q 1 by the first control circuit 5 .

The first control circuit 5 includes a first control unit 12 and a second control unit 13 . The first control unit 12 is configured to control the turning on and off of the main switching element Q 1 . A first control IC or the like can be used as the first control unit 12 , for example. The second control unit 13 is configured to control the first control unit 12 . A microcomputer or the like can be used as the second control unit 13 , for example.

The first control unit 12 is connected to the gate terminal of the main switching element Q 1 . Also, the first control unit 12 is connected to the source terminal of the main switching element Q 1 . Furthermore, the first control unit 12 is connected to the low potential side of the capacitor C 2 via the series circuit of the resistor R 5 and the resistor R 6 . In short, the first control unit 12 is configured to receive the first detection signal.

The second control unit 13 is connected to the anode of the diode D 2 . Also, the second control unit 13 is connected to the connection point of the resistor R 7 and the resistor R 8 . Furthermore, the second control unit 13 is connected to the connection point of the phase control circuit 11 and the power supply unit 1 . In short, the second control unit 13 is configured to receive the third detection signal and the power supply information signal.

The second control unit 13 is configured to, upon receiving the power supply information signal, generate the first control signal for controlling the first control unit 12 based on the power supply information (phase, in the present embodiment) of the power supply information signal. A first PWM (Pulse Width Modulation) signal or the like can be used as the first control signal, for example. The second control unit 13 includes a first storage unit. The first storage unit stores a first data table in which the power supply information of the power supply information signal is associated with a first duty ratio of the first control signal. The second control unit 13 is configured to generate the first control signal having the first duty ratio corresponding to the power supply information of the power supply information signal, according to the first data table.

Also, the second control unit 13 is configured to output the first control signal to the first control unit 12 . In short, the second control unit 13 is configured to output, to the first control unit 12 , the first control signal for controlling the first control unit 12 based on the power supply information of the power supply information signal.

The first control unit 12 is configured to control the turning on and off of the main switching element Q 1 based on the first duty ratio of the first control signal outputted from the second control unit 13 and the magnitude of the first detection signal. In one example, the first control unit 12 is configured to control the turning on and off of the main switching element Q 1 such that the output current I 1 of the conversion unit 2 is changed (the magnitude of the first detection signal is changed) in accordance with the first duty ratio of the first control signal outputted from the second control unit 13 . Accordingly, the power supply device 10 can perform light modulation of the light source unit 23 , for example, and can suppress fluctuation of the output current I 1 of the conversion unit 2 . Thus, the power supply device 10 can perform light modulation of the light source unit 23 , and can suppress flickering of light that is emitted from the light source unit 23 .

The second control unit 13 is configured to, when the magnitude of the third detection signal is a preset threshold value or more, stop the turning on and off of the main switching element Q 1 by the first control unit 12 , or stop operation of the conversion unit 2 . Accordingly, the power supply device 10 can, when a lightning surge is applied to the input voltage of the power supply unit 1 , for example, suppress an over current from flowing in the light source unit 23 . Note that, the threshold value is stored in advance in the first storage unit of the second control unit 13 .

The power supply device 10 includes a receiver 15 . The receiver 15 can receive a wireless signal from a wireless remote controller 24 , for example. Examples of the wireless signal include an infrared signal and a radio signal. In the power supply device 10 , a light modulation signal (second light modulation signal) is superimposed on the wireless signal. The second light modulation signal is a signal for instructing turning on, turning off, or performing light modulation of the solid-state light emitting elements 22 . A second PWM signal can be used as the second light modulation signal, for example.

The receiver 15 is electrically connected to the second control unit 13 . Also, the receiver 15 is configured to, upon receiving the wireless signal from the remote controller 24 , output the second light modulation signal that is superimposed on the wireless signal to the second control unit 13 . In short, the second control unit 13 is configured to receive the second light modulation signal for instructing the light modulation level of the solid-state light emitting elements 22 .

The second control unit 13 is configured to, upon receiving the second light modulation signal from the receiver 15 , generate the second control signal for controlling the first control unit 12 based on a second duty ratio of the second light modulation signal. A third PWM signal can be used as the second control signal, for example. The first storage unit of the second control unit 13 stores a second data table in which the second duty ratio of the second light modulation signal is associated with the third duty ratio of the second control signal. The second control unit 13 generates the second control signal having the third duty ratio corresponding to the second duty ratio of the second light modulation signal according to the second data table.

Also, the second control unit 13 is configured to output the second control signal to the first control unit 12 . In short, the second control unit 13 is configured to output, to the first control unit 12 , the second control signal for controlling the first control unit 12 based on the second duty ratio of the second light modulation signal.

The first control unit 12 is configured to control the turning on and off of the main switching element Q 1 based on the third duty ratio of the second control signal outputted from the second control unit 13 and the magnitude of the first detection signal. In other words, the first control unit 12 further includes a function for controlling the turning on and off of the main switching element Q 1 based on the third duty ratio of the second control signal outputted from the second control unit 13 and the magnitude of the first detection signal. In one example, the first control unit 12 is configured to, upon receiving the second control signal from the second control unit 13 , control the turning on and off of the main switching element Q 1 such that the output current I 1 of the conversion unit 2 is changed (the magnitude of the first detection signal is changed) in accordance with the third duty ratio of the second control signal. Accordingly, the power supply device 10 can perform light modulation of the light source unit 23 , for example, and can suppress the fluctuation of the output current I 1 of the conversion unit 2 . Thus, the power supply device 10 can perform light modulation of the light source unit 23 , and can suppress flickering of light that is emitted from the light source unit 23 . Note that, although the power supply device 10 includes the receiver 15 , the configuration is not particularly limited thereto. The power supply device 10 may not include the receiver 15 .

The first control circuit 5 includes a third control unit 14 . The third control unit 14 is configured to output an adjusting signal for adjusting the magnitude of the output current I 1 of the conversion unit 2 . A second control IC or the like can be used as the third control unit 14 , for example. The third control unit 14 is configured to output the adjusting signal based on the power supply information of the power supply information signal that was inputted to the second control unit 13 . The third control unit 14 is electrically connected to the second control unit 13 . The second control unit 13 is configured to, upon receiving the power supply information signal, output the power supply information signal to the third control unit 14 . The third control unit 14 includes a second storage unit. The second storage unit stores a third data table in which the power supply information (phase, in the present embodiment) of the power supply information signal is associated with the magnitude of the adjusting signal. The third control unit 14 is configured to output the adjusting signal corresponding to the power supply information of the power supply information signal according to the third data table. In one example, the third control unit 14 is configured to output the adjusting signal for adjusting the magnitude of the output current I 1 of the conversion unit 2 in accordance with the power supply information of the power supply information signal.

The first control unit 12 is configured to receive a fourth detection signal including the first detection signal and the adjusting signal. The third control unit 14 is connected to the resistor R 6 via a resistor R 9 . Also, the third control unit 14 is connected to the first control unit 12 via the resistor R 9 . In the power supply device 10 , the fourth detection signal is constituted by a signal in which the adjusting signal is superimposed on the first detection signal.

The first control unit 12 is configured to control the turning on and off of the main switching element Q 1 based on the magnitude of the fourth detection signal. In other words, the first control unit 12 further includes a function for controlling the turning on and off of the main switching element Q 1 based on the magnitude of the fourth detection signal. Accordingly, in the power supply device 10 , the output current I 1 of the conversion unit 2 can be changed arbitrarily.

Incidentally, the capacitance of the resonance capacitor C 1 and the inductance of the resonance inductor L 5 are each set such that, when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state, a waveform A 1 of a voltage (second voltage) V 2 that is generated between the drain terminal and the source terminal of the main switching element Q 1 takes a protruding curve shape (refer to FIG. 2 ), the voltage V 2 being generated due to a resonance phenomenon of at least the resonance capacitor C 1 , the primary winding L 1 , and the resonance inductor L 5 . The capacitance of the resonance capacitor C 1 is set such that a resonance voltage is generated in the primary winding L 1 of the transformer T 1 due to a resonance phenomenon of the resonance capacitor C 1 and an equivalent inductance of the primary winding L 1 and resonance inductor L 5 . Accordingly, in the power supply device 10 , a resonance voltage can be generated in the primary winding L 1 of the transformer T 1 when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state, and the output voltage V 1 of the conversion unit 2 can be boosted. Thus, in the power supply device 10 , the winding number of the secondary winding L 2 of the transformer T 1 can be reduced, and the transformer T 1 can be downsized. Therefore, the power supply device 10 can be downsized. Note that the capacitance of the resonance capacitor C 1 is set such that the resonance voltage is generated in the primary winding L 1 of the transformer T 1 due to a resonance phenomenon of the resonance capacitor C 1 and the equivalent inductance of the primary winding L 1 and resonance inductor L 5 , but the capacitance of the resonance capacitor C 1 can be set differently. The capacitance of the resonance capacitor C 1 may be set such that a resonance voltage is generated in the primary winding L 1 of the transformer T 1 due to a resonance phenomenon of the resonance capacitor C 1 and an equivalent inductance of the primary winding L 1 , resonance inductor L 5 , secondary winding L 2 , and leakage inductance of the transformer T 1 , for example. The waveform A 1 of the voltage V 2 of the main switching element Q 1 takes a protruding curve shape when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state. In other words, in the period S 2 (refer to FIG. 2 ), the waveform A 1 of the voltage V 2 of the main switching element Q 1 takes a waveform in which the voltage value of the voltage V 2 gradually increases according to the elapse of time and then gradually decreases according to the elapse of time after reaching a peak value of the voltage V 2 . That is to say, the voltage value of the voltage V 2 is larger at an intermediate point (time t 5 in FIG. 2 , for example) in the period S 2 than at the start point of the period S 2 (time t 3 in FIG. 2 , for example) or at the end point (time t 4 in FIG. 2 , for example).

In the power supply device 10 , a waveform A 2 of a current I 3 flowing in the sub switching element Q 2 takes an S shape (refer to FIG. 2 ) when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state. That is, the capacitance of the resonance capacitor C 1 and the inductance of the resonance inductor L 5 are each set such that the waveform A 2 of the current I 3 flowing in the sub switching element Q 2 takes an S shape when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state. The waveform A 2 of the current I 3 flowing in the sub switching element Q 2 takes an S shape when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state. In other words, in the period S 2 , the waveform A 2 of the current I 3 flowing in the sub switching element Q 2 takes a waveform in which the current value of the current I 3 flowing in the sub switching element Q 2 gradually changes from a negative maximum value to a positive maximum value according to the elapse of time. That is to say, the current value of the current I 3 is the negative maximum value at the start point (time t 2 in FIG. 2 , for example) of the period S 2 . The current value of the current I 3 gradually increases from the negative maximum value and becomes zero at the intermediate point (time t 5 in FIG. 2 , for example). Then, the current value of the current I 3 gradually increases from zero and becomes the positive maximum value at the end point (time t 4 in FIG. 2 , for example).

Also, the capacitance of the resonance capacitor C 1 and the inductance of the resonance inductor L 5 are each set such that, when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state, the peak value of the voltage V 2 of the main switching element Q 1 is greater than or equal to the output level V 3 of the power supply unit 1 and less than the breakdown voltage of the main switching element Q 1 . Accordingly, in the power supply device 10 , a switching element having a relatively low breakdown voltage can be selected as the main switching element Q 1 , and the output voltage V 1 of the conversion unit 2 can be boosted. Thus, downsizing and cost reduction of the power supply device 10 can be realized.

Hereinafter, operations of the power supply device 10 according to the present embodiment will be described with reference to FIGS. 1 and 2 . Note that, in the following, description will be given assuming that electric power is supplied to the power supply device 10 from a commercial power supply 25 . FIG. 2 shows a voltage V 4 across the resonance capacitor C 1 , a voltage V 5 between the gate and source of the sub switching element Q 2 , and a voltage V 6 between the drain and source of the sub switching element Q 2 .

When the main switching element Q 1 shifts from an off state to an on state (time t 1 , in FIG. 2 ) in the power supply device 10 , the current I 2 flows in the main switching element Q 1 via the primary winding L 1 of the transformer T 1 . Accordingly, in the power supply device 10 , magnetic energy is accumulated in the primary winding L 1 .

Also, when the main switching element Q 1 shifts from an on state to an off state (time t 2 , in FIG. 2 ) in the power supply device 10 , a counter-electromotive force is generated in the primary winding L 1 . Accordingly, in the power supply device 10 , the capacitor 8 is charged, and the voltage V 2 of the main switching element Q 1 increases (period from time t 2 to time t 3 , in FIG. 2 ). Also, when the capacitor 8 is charged (period from time t 3 to time t 4 , in FIG. 2 ) in the power supply device 10 , current flows in the diode 9 and the resonance capacitor C 1 is reverse-charged.

Also, when the resonance capacitor C 1 is reverse-charged in the power supply device 10 , the sub switching element Q 2 shifts from an off state to an on state if an induced voltage (voltage V 5 between the gate and source of the sub switching element Q 2 ) generated in the quaternary winding L 4 of the transformer T 1 becomes a gate threshold voltage Vth of the sub switching element Q 2 or more (time t 3 , in FIG. 2 ). Accordingly, in the power supply device 10 , the current I 3 flows in the sub switching element Q 2 from the primary winding L 1 via the resonance capacitor C 1 , and the waveform A 1 of the voltage V 2 of the main switching element Q 1 takes a protruding curve shape. Thus, in the power supply device 10 , the voltage V 2 of the main switching element Q 1 can be suppressed from increasing rapidly, and it is possible to suppress dielectric breakdown of the main switching element Q 1 . Also, in the power supply device 10 , the waveform A 2 of the current I 3 flowing in the sub switching element Q 2 takes an S shape, when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state.

Also, when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state (period from time t 3 to time t 4 , in FIG. 2 ) in the power supply device 10 , the resonance voltage is generated in the primary winding L 1 of the transformer T 1 due to a resonance phenomenon of at least the resonance capacitor C 1 , the primary winding L 1 , and the resonance inductor L 5 . Also, when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state in the power supply device 10 , the resonance voltage generated in the primary winding L 1 is transmitted to the secondary winding L 2 . Accordingly, in the power supply device 10 , a current I 4 flows in the resonance inductor L 5 , and the capacitor C 2 is charged. Thus, in the power supply device 10 , the light source unit 23 can be operated when the voltage across the capacitor C 2 becomes the sum of the forward voltages of the respective solid-state light emitting elements 22 or more.

Also, when the induced voltage generated in the quaternary winding L 4 of the transformer T 1 becomes less than the gate threshold voltage Vth of the sub switching element Q 2 (time t 4 , in FIG. 2 ) in the power supply device 10 , the sub switching element Q 2 shifts from an on state to an off state. Accordingly, in the power supply device 10 , charge accumulated in the resonance capacitor C 1 is discharged to ground via the power supply unit 1 . Also, in the power supply device 10 , charge accumulated in the capacitor 8 is discharged to ground via a path of the primary winding L 1 and the power supply unit 1 .

Incidentally, as shown in FIG. 3 , the inventors conceived a power supply device 16 , which is a simulation model of the power supply device 10 according to the present embodiment. The power supply unit 1 is a DC power supply that outputs a fixed DC voltage. Note that, in the power supply device 16 , constituent elements similar to those of the power supply device 10 are provided with the same reference numerals, and description thereof will be omitted as appropriate. A capacitor 17 in FIG. 3 represents a parasitic capacitor in the sub switching element Q 2 . Also, the graphic symbol of the switching elements Q 1 and Q 2 in FIG. 3 represents MOSFET in a simplified manner.

In the power supply device 16 , the output voltage of the power supply unit 1 is set to 140 V, the switching frequency of the main switching element Q 1 is set to 200 kHz, and the switching frequency of the sub switching element Q 2 is set to 200 kHz, but the values of these parameters are not specifically limited. The duty ratios of the switching elements Q 1 and Q 2 are each set to 38%, as an example.

Also, the inventors performed simulations by changing the capacitance of the resonance capacitor C 1 in the power supply device 16 , with the constants of circuit components other than the resonance capacitor C 1 being fixed. Note that the inventors used a circuit simulator or the like when the simulation was performed on the power supply device 16 , for example.

In the case where the capacitance of the resonance capacitor C 1 was set to 100 nF in the power supply device 16 , a waveform A 3 of a voltage V 7 between the drain and source of the main switching element Q 1 was flat, as shown in FIG. 4 , when the main switching element Q 1 was in an off state and the sub switching element Q 2 was in an on state. The peak value of the voltage V 7 was 246.6 V. The average value of an output current I 5 of the conversion unit 2 was 151.1 mA. FIG. 4 further shows a current I 6 flowing in the main switching element Q 1 , a voltage V 8 between the drain and source of the sub switching element Q 2 , and a current I 7 flowing in the sub switching element Q 2 .

Also, in the case where the capacitance of the resonance capacitor C 1 was set to 10 nF in the power supply device 16 , a waveform A 4 of the voltage V 7 between the drain and source of the main switching element Q 1 took a protruding curve shape (hereinafter referred to as first protruding curve), as shown in FIG. 5 , when the main switching element Q 1 was in an off state and the sub switching element Q 2 was in an on state. The peak value of the voltage V 7 was 257.1 V. The average value of the output current I 5 of the conversion unit 2 was 149.8 mA. FIG. 5 further shows the current I 6 flowing in the main switching element Q 1 , the voltage V 8 between the drain and source of the sub switching element Q 2 , and the current I 7 flowing in the sub switching element Q 2 .

Also, in the case where the capacitance of the resonance capacitor C 1 was set to 1.5 nF in the power supply device 16 , a waveform A 5 of the voltage V 7 between the drain and source of the main switching element Q 1 took a protruding curve shape (hereinafter referred to as second protruding curve), as shown in FIG. 6 , when the main switching element Q 1 was in an off state and the sub switching element Q 2 was in an on state. The curvature of the second protruding curve was larger than the curvature of the first protruding curve. The peak value of the voltage V 7 was 426.1 V. The average value of the output current I 5 of the conversion unit 2 was 151.6 mA. FIG. 6 further shows the current I 6 flowing in the main switching element Q 1 , the voltage V 8 between the drain and source of the sub switching element Q 2 , and the current I 7 flowing in the sub switching element Q 2 .

Accordingly, in the cases where the capacitance of the resonance capacitor C 1 is set to 10 nF and 1.5 nF in the power supply device 16 , the waveform A 4 and the waveform A 5 of the voltage V 7 take protruding curve shapes, and the peak values of the voltage V 7 are larger than that in the case where the capacitance of the resonance capacitor C 1 is set to 100 nF. Accordingly, in the power supply device 16 , in the case where the capacitance of the resonance capacitor C 1 is sufficiently smaller than the capacitance of the resonance capacitor C 1 in the case where the waveform A 3 of the voltage V 7 is flat, the waveforms A 4 and A 5 of the voltage V 7 can take protruding curve shapes, and the peak value of the voltage V 7 can be made large. That is to say, in the power supply device 10 , in the case where the capacitance of the resonance capacitor C 1 is sufficiently smaller than the capacitance of the resonance capacitor C 1 in the case where the waveform of the voltage V 2 is flat, the waveform of the voltage V 2 takes a protruding curve shape, and the peak value of the voltage V 2 can be made large. The capacitance being sufficiently smaller than the capacitance of the resonance capacitor C 1 in the case where the waveform of the voltage V 2 is flat is preferably a capacitance in a range from 1/100 to 1/10 of the capacitance of the resonance capacitor C 1 in the case where the waveform of the voltage V 2 is flat, for example. Note that, in the following description, the capacitance of the resonance capacitor C 1 being sufficiently smaller than the capacitance of the resonance capacitor C 1 in the case where the waveform A 3 of the voltage V 7 is flat is simply referred to as “the capacitance of the resonance capacitor C 1 being sufficiently small”, for the sake of description.

FIG. 7 is an example of the simulation result performed on the power supply device 16 , and shows a correlation diagram between the winding ratio of the transformer T 1 and the capacitance of the resonance capacitor C 1 , in the cases where the average value of the output current I 5 of the conversion unit 2 is set to 150 mA and 75 mA. The winding ratio of the transformer T 1 is the ratio of the winding number of the secondary winding L 2 relative to the winding number of the primary winding L 1 . The curve designated by B 1 in FIG. 7 is a simulation result in the case where the average value of the output current I 5 of the conversion unit 2 is 150 mA. Also, the curve designated by B 2 in FIG. 7 is a simulation result in the case where the average value of the output current I 5 of the conversion unit 2 is 75 mA.

The winding ratio of the transformer T 1 was 0.58 when the capacitance of the resonance capacitor C 1 was set to 10 nF and the average value of the output current I 5 of the conversion unit 2 was 150 mA in the power supply device 16 . The winding ratio of the transformer T 1 was 0.575 when the capacitance of the resonance capacitor C 1 was set to 4.7 nF and the average value of the output current I 5 of the conversion unit 2 was 150 mA in the power supply device 16 . The winding ratio of the transformer T 1 was 0.518 when the capacitance of the resonance capacitor C 1 was set to 2.2 nF and the average value of the output current I 5 of the conversion unit 2 was 150 mA in the power supply device 16 . The winding ratio of the transformer T 1 was 0.462 when the capacitance of the resonance capacitor C 1 was set to 1.5 nF and the average value of the output current I 5 of the conversion unit 2 was 150 mA in the power supply device 16 . The winding ratio of the transformer T 1 was 0.42 when the capacitance of the resonance capacitor C 1 was set to 1.2 nF and the average value of the output current I 5 of the conversion unit 2 was 150 mA in the power supply device 16 . The winding ratio of the transformer T 1 was 0.382 when the capacitance of the resonance capacitor C 1 was set to 1 nF and the average value of the output current I 5 of the conversion unit 2 was 150 mA in the power supply device 16 .

Also, the winding ratio of the transformer T 1 was 0.479 when the capacitance of the resonance capacitor C 1 was set to 10 nF and the average value of the output current I 5 of the conversion unit 2 was 75 mA in the power supply device 16 . The winding ratio of the transformer T 1 was 0.472 when the capacitance of the resonance capacitor C 1 was set to 4.7 nF and the average value of the output current I 5 of the conversion unit 2 was 75 mA in the power supply device 16 . The winding ratio of the transformer T 1 was 0.43 when the capacitance of the resonance capacitor C 1 was set to 2.2 nF and the average value of the output current I 5 of the conversion unit 2 was 75 mA in the power supply device 16 . The winding ratio of the transformer T 1 was 0.385 when the capacitance of the resonance capacitor C 1 was set to 1.5 nF and the average value of the output current I 5 of the conversion unit 2 was 75 mA in the power supply device 16 . The winding ratio of the transformer T 1 was 0.352 when the capacitance of the resonance capacitor C 1 was set to 1.2 nF and the average value of the output current I 5 of the conversion unit 2 was 75 mA in the power supply device 16 . The winding ratio of the transformer T 1 was 0.32 when the capacitance of the resonance capacitor C 1 was set to 1 nF and the average value of the output current I 5 of the conversion unit 2 was 75 mA in the power supply device 16 .

Accordingly, in the power supply device 16 , the winding number of the secondary winding L 2 of the transformer T 1 can be reduced in the case where the winding number of the primary winding L 1 of the transformer T 1 is fixed and the capacitance of the resonance capacitor C 1 is set to a value that is sufficiently small. That is to say, in the power supply device 10 , the winding number of the secondary winding L 2 of the transformer T 1 can be reduced in the case where the winding number of the primary winding L 1 of the transformer T 1 is fixed and the capacitance of the resonance capacitor C 1 is set to a value that is sufficiently small. Thus, in the power supply device 10 , the transformer T 1 can be downsized.

In the power supply device 10 , in the case where the capacitance of the resonance capacitor C 1 is set to a value that is sufficiently small, the waveform A 1 of the voltage V 2 of the main switching element Q 1 takes a protruding curve shape, and the peak value of the voltage V 2 can be increased. Also, in the power supply device 10 , in the case where the capacitance of the resonance capacitor C 1 is set to a value that is sufficiently small, the winding number of the secondary winding L 2 of the transformer T 1 can be reduced, and the transformer T 1 can be downsized.

Also, in the power supply device 10 , the secondary winding L 2 is connected in series to the series circuit of the rectifying element 4 and the resonance inductor L 5 . In the power supply device 10 , the capacitance of the resonance capacitor C 1 and the inductance of the resonance inductor L 5 are each set such that, when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state, the waveform A 1 of the voltage V 2 of the main switching element Q 1 takes a protruding curve shape, the voltage V 2 being generated due to a resonance phenomenon of at least the resonance capacitor C 1 , the primary winding L 1 , and the resonance inductor L 5 . Accordingly, in the power supply device 10 , a voltage doubler half-wave rectifying circuit in a power supply device 70 that includes a configuration shown in FIG. 12 , which serves as a comparative example, is not needed, and further downsizing can be realized compared with the power supply device 70 serving as the comparative example.

The power supply device 10 according to the present embodiment as described above includes the power supply unit 1 , the conversion unit 2 , and the control unit 3 . The power supply unit 1 is configured to generate the first DC voltage from an input voltage. The conversion unit 2 is configured to convert the first DC voltage outputted from the power supply unit 1 into the second DC voltage having a different voltage value. The control unit 3 is configured to control the conversion unit 2 . The conversion unit 2 is an active clamp type flyback converter. The conversion unit 2 includes the main switching element Q 1 , the sub switching element Q 2 , the flyback transformer T 1 , and the rectifying element 4 . The transformer T 1 includes the primary winding L 1 and the secondary winding L 2 . The rectifying element 4 is configured to half-wave rectify the first voltage generated in the secondary winding L 2 . The main switching element Q 1 and the sub switching element Q 2 each include the first main terminal, the second main terminal, and the control terminal. The primary winding L 1 is connected in series to the main switching element Q 1 , and is connected in parallel to the series circuit of the resonance capacitor C 1 and the sub switching element Q 2 . The secondary winding L 2 is connected in series to the series circuit of the rectifying element 4 and the resonance inductor L 5 . The control unit 3 is configured to control the main switching element Q 1 and the sub switching element Q 2 . The control unit 3 includes a first control mode, the second control mode, and the third control mode, as the control modes. The first control mode is a mode in which the main switching element Q 1 is put in an on state, and the sub switching element Q 2 is put in an off state. The second control mode is a mode in which the main switching element Q 1 is put in an off state, and the sub switching element Q 2 is put in an on state. The third control mode is a mode in which the main switching element Q 1 and the sub switching element Q 2 are both put in the off state. The control unit 3 is configured to alternate between the first control mode and the second control mode via the third control mode. The capacitance of the resonance capacitor C 1 and the inductance of the resonance inductor L 5 are each set such that, in the period S 2 in which the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state, the waveform A 1 , with respect to time in the period S 2 , of the voltage V 2 that is generated between the first main terminal (drain terminal) and the second main terminal (source terminal) of the main switching element Q 1 takes a protruding curve shape, the second voltage (voltage V 2 ) being generated due to a resonance phenomenon of at least the resonance capacitor C 1 , the primary winding L 1 , and the resonance inductor L 5 .

Accordingly, in the power supply device 10 , when the main switching element Q 1 is in an off state, and the sub switching element Q 2 is in an on state, a resonance voltage can be generated in the primary winding L 1 of the transformer T 1 and the output voltage V 1 of the conversion unit 2 can be boosted. Thus, in the power supply device 10 , the winding number of the secondary winding L 2 of the transformer T 1 can be reduced, and the transformer T 1 can be downsized, and further downsizing of the power supply device 10 can be realized compared with the power supply device 70 serving as the comparative example. Also, in the power supply device 10 , a switching element having a relatively low breakdown voltage can be selected as the main switching element Q 1 , and the transformer T 1 can be downsized.

In other words, in the power supply device 10 , the capacitance of the resonance capacitor C 1 and the inductance of the resonance inductor L 5 are each set such that, when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state, the waveform A 1 of the voltage V 2 that is generated between the first main terminal and the second main terminal of the main switching element Q 1 takes a protruding curve shape, the voltage V 2 being generated due to a resonance phenomenon of at least the resonance capacitor C 1 , the primary winding L 1 , and the resonance inductor L 5 . Accordingly, in the power supply device 10 , when the main switching element Q 1 is in an off state, and the sub switching element Q 2 is in an on state, a resonance voltage can be generated in the primary winding L 1 of the transformer T 1 and the output voltage V 1 of the conversion unit 2 can be boosted. Accordingly, in the power supply device 10 , the winding number of the secondary winding L 2 of the transformer T 1 can be reduced, and the transformer T 1 can be downsized. Thus, the power supply device 10 can be further downsized.

Also, in the power supply device 10 , the control unit 3 is configured to alternate between the first control mode and the second control mode via the third control mode. Accordingly, in the power supply device 10 , soft switching of the switching elements Q 1 and Q 2 can be performed. Accordingly, in the power supply device 10 , switching losses of the switching elements Q 1 and Q 2 can be suppressed. Also, in the power supply device 10 , since the soft switching of the switching elements Q 1 and Q 2 can be performed, the generation of noise can be suppressed. Thus, in the power supply device 10 , a noise filter or the like is not needed, for example, and further downsizing can be realized.

Also, in the power supply device 10 , when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state, the waveform A 1 of the voltage V 2 that is generated between the first main terminal and the second main terminal of the main switching element Q 1 takes a protruding curve shape, the voltage V 2 being generated due to a resonance phenomenon of at least the resonance capacitor C 1 , the primary winding L 1 , and the resonance inductor L 5 . Accordingly, in the power supply device 10 , a harmonic component of the voltage V 2 that is generated between the first main terminal and the second main terminal of the main switching element Q 1 can be suppressed, and generation of noise can be suppressed. Thus, in the power supply device 10 , a noise filter or the like is not needed, for example, and further downsizing can be realized.

Also, in the power supply device 10 , the secondary winding L 2 is connected in series to the series circuit of the rectifying element 4 and the resonance inductor L 5 . Accordingly, in the power supply device 10 , the current I 4 flowing in the resonance inductor L 5 can be made constant, for example, and flickering of light emitted from the light source unit 23 can be suppressed.

The capacitance of the resonance capacitor C 1 and the inductance of the resonance inductor L 5 are each set such that, in the period S 2 in which the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state, the waveform A 2 , with respect to time in the period S 2 , of the current I 3 flowing in the sub switching element Q 2 takes an S shape. Accordingly, in the power supply device 10 , a switching element having a relatively low breakdown voltage can be selected as the main switching element Q 1 , and the transformer T 1 can be downsized.

The capacitance of the resonance capacitor C 1 and the inductance of the resonance inductor L 5 are each set such that, when the main switching element Q 1 is in an off state and the sub switching element Q 2 is in an on state, the peak value of the second voltage (voltage V 2 ) that is generated between the first main terminal and the second main terminal of the main switching element Q 1 is greater than or equal to the output level V 3 of the power supply unit 1 and less than the breakdown voltage of the main switching element Q 1 . Accordingly, in the power supply device 10 , it is possible to suppress the case where the peak value of the voltage V 2 of the main switching element Q 1 becomes the breakdown voltage of the main switching element Q 1 or more.

The control unit 3 is configured to control the conversion unit 2 such that the output current I 1 of the conversion unit 2 is made constant. Accordingly, in the power supply device 10 , fluctuation of the output current I 1 of the conversion unit 2 can be suppressed. Thus, in the case where the power supply device 10 supplies electric power to the light source unit 23 , for example, flickering of light emitted from the light source unit 23 can be suppressed.

It is preferable that the coupling coefficient of the transformer T 1 is in a range of 0.9 to 1 inclusive. Accordingly, in the power supply device 10 , further downsizing of the transformer T 1 can be realized compared with the case in which the coupling coefficient of the transformer T 1 is less than 0.9.

The control unit 3 includes the first control circuit 5 and the second control circuit 6 . The first control circuit 5 is configured to control the main switching element Q 1 . The second control circuit 6 is configured to control the sub switching element Q 2 . The tertiary winding L 3 and the quaternary winding L 4 are provided on the primary side of the transformer T 1 . The tertiary winding L 3 and the quaternary winding L 4 are magnetically coupled to the primary winding L 1 . The first control circuit 5 employs a voltage generated in the tertiary winding L 3 as an operation power supply. The first control circuit 5 is configured to control the main switching element Q 1 based on the magnitude of the output current I 1 of the conversion unit 2 . The second control circuit 6 is configured to control the sub switching element Q 2 based on the magnitude of the voltage generated in the quaternary winding L 4 .

Accordingly, in the power supply device 10 , the first control circuit 5 can control the main switching element Q 1 according to the output current I 1 of the conversion unit 2 . Also, in the power supply device 10 , the second control circuit 6 can control the sub switching element Q 2 according to current flowing in the primary winding L 1 .

The second control circuit 6 is a self-excited type control circuit. The second control circuit 6 is configured to turn on and off the sub switching element Q 2 in coordination with the turning on and off of the main switching element Q 1 by the first control circuit 5 . Accordingly, the power supply device 10 can be downsized compared with a case where the second control circuit 6 is a separately excited type control circuit.

The first control circuit 5 is configured to receive the first detection signal, the second detection signal, and the power supply information signal. The first detection signal corresponds to the output current I 1 of the conversion unit 2 . The second detection signal corresponds to the current I 2 flowing in the main switching element Q 1 . The power supply information signal includes power supply information. The power supply information includes at least one of a waveform of the input voltage of the power supply unit 1 , an amplitude in the waveform of the input voltage, and a phase in the waveform of the input voltage.

Accordingly, the first control circuit 5 can control the main switching element Q 1 such that the output current I 1 of the conversion unit 2 is changed, for example, based on at least one of the first detection signal, the second detection signal, and the power supply information signal.

The first control circuit 5 is configured to receive the third detection signal corresponding to the output voltage V 1 of the conversion unit 2 . The third detection signal corresponds to the output voltage V 1 of the conversion unit 2 . The first control circuit 5 is configured to control the main switching element Q 1 based on the magnitude of the third detection signal. Accordingly, the first control circuit 5 can suppress an over-voltage from being applied to the light source unit 23 , for example.

The phase control circuit 11 is electrically connected to the input side of the power supply unit 1 . The phase control circuit 11 performs phase control on the sine wave-like AC voltage. The power supply unit 1 is configured to generate the first DC voltage from the voltage on which phase control is performed by the phase control circuit 11 as the input voltage. Accordingly, the power supply device 10 can use the voltage on which phase control is performed by the phase control circuit 11 as the operation power supply.

The phase control circuit 11 is configured to perform light modulation of the solid-state light emitting element 22 that is to be electrically connected to the output side of the conversion unit 2 . Accordingly, the power supply device 10 can perform light modulation of the solid-state light emitting elements 22 in the case where the light source unit 23 is connected to the output side of the conversion unit 2 , for example.

The first control circuit 5 is configured to receive the power supply information signal. The power supply information signal includes the power supply information. The power supply information includes at least one of the waveform of the input voltage of the power supply unit 1 , the amplitude in the waveform of the input voltage, and the phase in the waveform of the input voltage. The power supply information signal is the first light modulation signal for instructing the light modulation level of the solid-state light emitting element 22 , and is constituted by the waveform of the voltage on which phase control was performed by the phase control circuit 11 . Accordingly, in the case where the light source unit 23 is connected to the output side of the conversion unit 2 , for example, the first control circuit 5 can perform light modulation of the solid-state light emitting elements 22 by controlling the main switching element Q 1 based on the power supply information (phase) of the power supply information signal.

The first control circuit 5 includes the first control unit 12 and the second control unit 13 . The first control unit 12 is configured to control the turning on and off of the main switching element Q 1 . The second control unit 13 is configured to control the first control unit 12 . The first control unit 12 is configured to receive the first detection signal. The first detection signal corresponds to the output current I 1 of the conversion unit 2 . The second control unit 13 is configured to receive the power supply information signal, and to output the first control signal for controlling the first control unit 12 based on the power supply information of the power supply information signal to the first control unit 12 . The power supply information signal includes the power supply information. The power supply information includes at least one of the waveform of the input voltage of the power supply unit 1 , the amplitude in the waveform of the input voltage, and the phase in the waveform of the input voltage. The first control signal is the first PWM signal. The first control unit 12 is configured to control the turning on and off of the main switching element Q 1 based on the first duty ratio of the first control signal outputted from the second control unit 13 and the magnitude of the first detection signal.

Accordingly, the first control unit 12 can control the turning on and off of the main switching element Q 1 based on the first duty ratio of the first control signal and the magnitude of the first detection signal. Thus, the power supply device 10 can perform light modulation of the light source unit 23 based on the power supply information (phase) of the power supply information signal outputted from the light modulator that is used as the phase control circuit 11 , for example.

The second control unit 13 is configured to receive the third detection signal. The third detection signal corresponds to the output voltage V 1 of the conversion unit 2 . The second control unit 13 is configured to, when the magnitude of the third detection signal is the predetermined threshold value or more, stop the turning on and off of the main switching element Q 1 by the first control unit 12 , or stop the operation of the conversion unit 2 . Accordingly, the power supply device 10 can suppress an over current from flowing in the light source unit 23 , for example.

The second control unit 13 is configured to receive the second light modulation signal for instructing the light modulation level of the solid-state light emitting element 22 that is to be electrically connected to the output side of the conversion unit 2 . The second light modulation signal is the second PWM signal. The second control unit 13 is configured to output the second control signal for controlling the first control unit 12 based on the second duty ratio of the second light modulation signal to the first control unit 12 . The second control signal is the third PWM signal. The first control unit 12 further includes the function for controlling the turning on and off of the main switching element Q 1 based on the third duty ratio of the second control signal outputted from the second control unit 13 and the magnitude of the first detection signal.

Accordingly, the first control unit 12 can control the turning on and off of the main switching element Q 1 based on the third duty ratio of the second control signal and the magnitude of the first detection signal. Thus, the power supply device 10 can perform light modulation of the light source unit 23 based on the second duty ratio of the second light modulation signal that is superimposed on the wireless signal described above from the remote controller 24 , for example.

The first control circuit 5 includes the third control unit 14 . The third control unit 14 is configured to output the adjusting signal for adjusting the magnitude of the output current I 1 of the conversion unit 2 based on the power supply information of the power supply information signal that was inputted to the second control unit 13 . The first control unit 12 is configured to receive the fourth detection signal that includes the first detection signal and the adjusting signal. The first control unit 12 further includes the function for controlling the turning on and off of the main switching element Q 1 based on the magnitude of the fourth detection signal. Accordingly, in the power supply device 10 , the output current I 1 of the conversion unit 2 can be arbitrarily changed.

Hereinafter, an example of a lighting apparatus 30 including the power supply device 10 according to the present embodiment will be briefly described with reference to FIGS. 8 and 9 .

The lighting apparatus 30 is configured to be attached directly to a ceiling member 40 , for example. The lighting apparatus 30 includes the power supply device 10 and the light source unit 23 including the two or more solid-state light emitting elements 22 that can be turned on by the power supply device 10 .

The light source unit 23 includes the solid-state light emitting elements 22 and a mounting substrate 26 . A printed wiring board or the like can be used as the mounting substrate 26 , for example. The solid-state light emitting elements 22 are mounted on a first face side (lower face side, in FIG. 8 ) of the mounting substrate 26 . The solid-state light emitting elements 22 are arranged at equal intervals on a circumference of a virtual circle on the first face of the mounting substrate 26 . The mounting substrate 26 is electrically connected to the power supply device 10 via a pair of first connection lines. Note that the solid-state light emitting elements 22 and the mounting substrate 26 are not shown in FIG. 9 .

Also, the lighting apparatus 30 includes an apparatus body 31 and a diffusion part 32 . The power supply device 10 and the light source unit 23 are attached to the apparatus body 31 . The diffusion part 32 diffuses light emitted from the solid-state light emitting elements 22 .

The apparatus body 31 includes a main body 33 having a bottomed tubular shape (a bottomed cylindrical shape, in the present embodiment) and a flange portion 34 that protrudes outward from an end portion of a side wall, on an opening side (lower side, in FIG. 8 ), of the main body 33 . Metal (iron, aluminum, stainless steel, or the like, for example) or the like can be used as the material of the apparatus body 31 , for example.

A first hole for the passage of a pair of second connection lines 35 and 36 that is electrically connected to the commercial power supply 25 (refer to FIG. 1 ) is formed in a bottom wall of the main body 33 . The pair of second connection lines 35 and 36 is led out through a second hole 41 provided in advance in the ceiling member 40 . The pair of second connection lines 35 and 36 is electrically connected to the power supply device 10 in the lighting apparatus 30 .

A translucent material (acrylic resin, glass, or the like, for example) or the like can be used as the material of the diffusion part 32 , for example. The diffusion part 32 is detachably attached to the flange portion 34 of the apparatus body 31 .

A screw or the like is used as a means for directly attaching the apparatus body 31 to the ceiling member 40 in the lighting apparatus 30 , for example. A third hole is formed in the bottom wall of the main body 33 for the passage of the screw. Accordingly, the apparatus body 31 in the lighting apparatus 30 can be directly attached to the ceiling member 40 .

The lighting apparatus 30 according to the present embodiment, as described above, includes the power supply device 10 , the light source unit 23 including the solid-state light emitting element 22 that can be turned on by the power supply device 10 , and the apparatus body 31 to which the power supply device 10 and the light source unit 23 are attached. Accordingly, the lighting apparatus 30 can be further downsized.

A power supply device 20 according to the present embodiment differs from the power supply device 10 according to the Embodiment 1 in that, as shown in FIGS. 10 and 11 , a power factor improving circuit 18 for improving a power factor of a voltage (full-wave rectified voltage) resulting from full-wave rectification of a sine wave shaped AC voltage is electrically connected to an input side of a power supply unit 1 . The basic configuration of the power supply device 20 according to the present embodiment is similar to the power supply device 10 according to the Embodiment 1. Note that, in the present embodiment, constituent elements similar to those in Embodiment 1 are provided with the same reference numerals, and description thereof will be omitted as appropriate.

The power supply unit 1 is configured to generate a first DC voltage using an output voltage of the power factor improving circuit 18 as an input voltage.

A rectifying circuit 19 configured to full-wave-rectify the sine wave shaped AC voltage is electrically connected to an input side of the power factor improving circuit 18 . The rectifying circuit 19 full-wave-rectifies the sine wave shaped AC voltage. A commercial power supply 25 is electrically connected to an input side of the rectifying circuit 19 , for example. Note that a wall switch is provided in a power supply path between the rectifying circuit 19 and the commercial power supply 25 . The wall switch is configured to turn on and off power supply from the commercial power supply 25 to the power supply device 20 .

A diode bridge, as shown in FIG. 11 , or the like can be used as the rectifying circuit 19 , for example. A pair of input terminals 19 a and 19 b of the diode bridge used as the rectifying circuit 19 is connected to the commercial power supply 25 . A pair of output terminals 19 c and 19 d of the diode bridge used as the rectifying circuit 19 is connected to the power factor improving circuit 18 .

A smoothing circuit configured to smooth a trough in a waveform of the full-wave rectified voltage resulting from full-wave rectification by the rectifying circuit 19 can be used as the power factor improving circuit 18 , for example. The smoothing circuit includes three diodes D 3 to D 5 and two capacitors C 5 and C 6 , as shown in FIG. 11 , for example. In short, the power factor improving circuit 18 is a smoothing circuit that smoothes a trough in a waveform of the full-wave rectified voltage resulting from full-wave rectification by the rectifying circuit 19 , and includes two or more diodes D 3 to D 5 (three, in the present embodiment) and two or more capacitors C 5 and C 6 (two, in the present embodiment).

A series circuit of the capacitor C 5 and the diode D 3 is connected between the pair of output terminals 19 c and 19 d of the rectifying circuit 19 . A high potential side of the capacitor C 5 is connected to the output terminal 19 c of the rectifying circuit 19 . A low potential side of the capacitor C 5 is connected to a cathode of the diode D 3 . An anode of the diode D 3 is connected to the output terminal 19 d of the rectifying circuit 19 .

A series circuit of the diode D 4 and the capacitor C 6 is connected between a connection point P 1 of the high potential side of the capacitor C 5 and the output terminal 19 c of the rectifying circuit 19 and a connection point P 2 of the anode of the diode D 3 and the output terminal 19 d of the rectifying circuit 19 . A cathode of the diode D 4 is connected to the connection point P 1 . An anode of the diode D 4 is connected to the connection point P 2 via the capacitor C 6 .

The diode D 5 is connected between a connection point P 3 of the capacitor C 5 and the diode D 3 and a connection point P 4 of the diode D 4 and the capacitor C 6 . An anode of the diode D 5 is connected to the connection point P 3 . A cathode of the diode D 5 is connected to the connection point P 4 .

In the power factor improving circuit 18 , an output current I 8 from the output terminal 19 c of the rectifying circuit 19 flows to the output terminal 19 d of the rectifying circuit 19 via a path constituted by the capacitor C 5 , the diode D 5 , and the capacitor C 6 . In the power factor improving circuit 18 , the capacitor C 5 and the capacitor C 6 are set to have the same capacitance. Accordingly, in the power factor improving circuit 18 , the capacitor C 5 and the capacitor C 6 are each charged in a period in which the voltage value of the full-wave rectified voltage resulting from full-wave rectification by the rectifying circuit 19 is relatively large.

The capacitor C 5 and the capacitor C 6 each discharge a charged voltage V 9 charged in each of the capacitors C 5 and C 6 to the high potential side of the power factor improving circuit 18 in a period in which the voltage value of the full-wave rectified voltage is relatively small. Accordingly, the power factor improving circuit 18 can smooth a trough in the waveform of the voltage resulting from full-wave rectification. That is, the power factor improving circuit 18 is configured to smooth a trough in the waveform of the full-wave rectified voltage resulting from full-wave rectification by the rectifying circuit 19 .

Note that, although the smoothing circuit is used as the power factor improving circuit 18 in the present embodiment, the power factor improving circuit 18 is not limited to the smoothing circuit. Also, although the power factor improving circuit 18 is provided on the input side of the power supply unit 1 in the present embodiment, the power factor improving circuit 18 is not limited to being provided on the input side of the power supply unit 1 . Also, the power factor improving circuit 18 need not be provided to the power supply device 20 . In this case, it is preferable that an AC/DC converter or the like is used as the power supply unit 1 , for example.

In the power supply device 20 according to the present embodiment described above, the power factor improving circuit 18 is electrically connected to the input side of the power supply unit 1 . The power factor improving circuit 18 improves the power factor of the full-wave rectified voltage resulting from full-wave rectification of the sine wave shaped AC voltage. The power supply unit 1 is configured to generate the first DC voltage using an output voltage of the power factor improving circuit 18 as the input voltage.

Accordingly, a higher power factor can be obtained in the power supply device 20 compared with the case where the power factor improving circuit 18 is not connected to the input side of the power supply unit 1 . Thus, the power supply device 20 can satisfy the harmonic regulations (Japanese Industrial Standards JIS C 61000-3-2, for example).

Also, in the power supply device 20 , the rectifying circuit 19 is electrically connected to the input side of the power factor improving circuit 18 . The rectifying circuit 19 full-wave rectifies the sine wave shaped AC voltage. The power factor improving circuit 18 is a smoothing circuit that smoothes the trough in the waveform of the full-wave rectified voltage resulting from full-wave rectification by the rectifying circuit 19 . Accordingly, a high power factor can be obtained in the power supply device 20 with a simple configuration.

Note that the power supply device 20 according to the present embodiment may be applied to the lighting apparatus 30 according to Embodiment 1, for example.

While the foregoing has described what are considered to be the best mode and/or other examples, it is understood that various modifications may be made therein and that the subject matter disclosed herein may be implemented in various forms and examples, and that they may be applied in numerous applications, only some of which have been described herein. It is intended by the following claims to claim any and all modifications and variations that fall within the true scope of the present teachings.