Light emitting diode (LED) driver having direct replacement capabilities

The present disclosure relates generally to a driver circuit for powering a load, and more particularly to a driver circuit connectable to a fluorescent ballast including over current, over temperature, and over voltage protection.

Light emitting diode (LED) based lighting systems may offer several energy and reliability advantages over other types of lighting systems such as, for example, incandescent or fluorescent lighting. Thus, LED based lighting systems may be used to replace other existing lighting technologies. Fluorescent tube lighting has historically been a significant source of illumination in many applications, particularly in commercial markets, for a number of reasons. However, fluorescent lights are typically unable to run directly from alternating current (AC). To make fluorescent lighting practical and relatively easy to use, a ballast may be placed between AC mains power and a fluorescent tube light in order to control and regulate the voltage, current and power.

Conversion from fluorescent tube lighting to newer technologies, such as LED based lighting systems, may become costly due to characteristics that are fundamentally associated with fluorescent lighting. In particular, conversion from fluorescent tube lighting to LED tube lighting usually requires the fluorescent tube light and as well as the ballast used to control power to the fluorescent tube light to be removed first. Then the LED tube light, which does not typically require a ballast, is subsequently installed. Some individuals may find it cumbersome and time consuming to remove the ballast first before the LED tube light may be installed. Accordingly, there is a continuing need in the art for an more efficient approach to retrofit fluorescent tube lighting with LED tube lighting.

In one embodiment, a driver circuit for powering a load is disclosed. The driver circuit includes an input for connection to a ballast, a rectifier, a switch, and a fault circuit. The rectifier converts AC power received from the input into DC power. The rectifier includes a rectifier input. The switch is electrically connected to the rectifier input. The switch is activated to create a short circuit at the rectifier inputs in response to receiving an activation signal. The fault circuit is electrically connected to the switch. The fault circuit generates the activation signal in response to detecting at least one of an over voltage, an over temperature, and an over current condition of the driver circuit.

In another embodiment, a driver circuit for powering a load is disclosed. The driver circuit includes an input for connection to a ballast, a rectifier, a switch, a fault circuit, and a charge pump circuit. The rectifier converts AC power received from the input into DC power. The rectifier includes a rectifier input. The switch is electrically connected to the rectifier input. The switch is activated to create a short circuit at the rectifier inputs in response to receiving an activation signal. The fault circuit is electrically connected to the switch. The fault circuit generates the activation signal in response to detecting at least one of an over voltage, an over temperature, and an over current condition of the driver circuit. The charge pump circuit provides substantially constant DC current to the fault circuit.

In yet another embodiment, a lighting system is disclosed. The lighting system includes a fluorescent ballast, a light emitting diode (LED) tube light, and a driver circuit for powering the LED tube light. The driver circuit includes an input for connection to a ballast, a rectifier, a switch, and a fault circuit. The rectifier converts AC power received from the input into DC power. The rectifier includes a rectifier input. The switch is electrically connected to the rectifier input. The switch is activated to create a short circuit at the rectifier inputs in response to receiving an activation signal. The fault circuit is electrically connected to the switch. The fault circuit generates the activation signal in response to detecting at least one of an over voltage, an over temperature, and an over current condition of the driver circuit.

FIG. 1 is an exemplary block diagram of a lighting system including a driver circuit for providing DC current to a load;

FIGS. 2A-2B are an exemplary circuit diagram of the driver circuit shown in FIG. 1 , where the circuit includes a switch that is a silicon controlled rectifier (SCR);

FIGS. 3A-3B are an alternative embodiment of the circuit diagram shown in FIGS. 2A-2B , where the switch shown in FIG. 2A is a metal-oxide-semiconductor field-effect transistor (MOSFET) and the driver circuit includes a latching circuit; and

FIGS. 4A-4B are an alternative embodiment of the circuit diagram shown in FIGS. 3A-3B , where the switch is a SCR.

The following detailed description will illustrate the general principles of the invention, examples of which are additionally illustrated in the accompanying drawings. In the drawings, like reference numbers indicate identical or functionally similar elements.

FIG. 1 is an exemplary block diagram of a lighting system 8 including a driver circuit 10 electrically connected to a fluorescent ballast 12 . The driver circuit 10 provides DC current to a load 18 . In the embodiment as illustrated, the load 18 is a light emitting diode (LED) tube light. However, it is to be understood that the disclosed driver circuit 10 may be used to power any other type of load requiring DC power as well. The driver circuit 10 may include a pair of power input lines 20 for connection to the fluorescent ballast 12 . The fluorescent ballast 12 may be electrically connected to a source (not shown) of AC power such as, for example, main power lines at a nominal 120 volts AC. The fluorescent ballast 12 may be used to control and regulate voltage, current and power to a fluorescent tube light (not illustrated). As explained in greater detail below, the driver circuit 10 eliminates the need for removing the fluorescent ballast 12 of the lighting system 8 when a fluorescent tube light (not illustrated) is replaced by solid state lighting (i.e., a LED tube light).

FIGS. 2A-2B are an exemplary circuit diagram of the driver circuit 10 shown in FIG. 1 . Referring to FIGS. 1-2A , the driver circuit 10 includes two current limiting capacitors C 1 and C 2 (shown in FIG. 2A ), a rectifier 26 , a DC filter 28 , a protection circuit 30 , a charge pump circuit 32 , an over voltage circuit 34 , an over temperature circuit 36 , and an over current circuit 38 . The over voltage circuit 34 , the over temperature circuit 36 , and the over current circuit 38 are part of a fault circuit 42 used to turn off or stop power from flowing through the driver circuit 10 during a fault condition, which is explained in greater detail below. The rectifier 26 may be in electrical communication with the current limiting capacitors C 1 and C 2 , and converts incoming AC power from the fluorescent ballast 12 to a pulsing DC power. Although the rectifier 26 is shown as a full wave diode bridge rectifier, those skilled in the art will readily appreciate that any type of full wave rectifier may be used as well.

The output of the rectifier 26 may be in electrical communication with the DC filter 28 . In the exemplary embodiment as shown in FIGS. 2A-2B , the a DC filter 28 may include a capacitor C 6 . Those of ordinary skill in the art will readily appreciate that the capacitor C 6 may be an electrolytic capacitor that acts as a smoothing capacitor. Specifically, the capacitor C 6 may be used to smoothen or reduce the amount of ripple in the DC power provided by the rectifier 26 such that relatively steady DC power may be provided to the remaining components within the driver circuit 10 .

The protection circuit 30 may include two diodes D 5 and D 6 , a switch Q 1 , and a resistor R 1 . The switch Q 1 includes an anode A and a cathode C, where the anode A is electrically connected to inputs 44 of the rectifier 26 and the diodes D 5 and D 6 direct current into the anode A of the switch Q 1 . A gate G may of the switch Q 1 may be electrically connected to the fault circuit 42 . As explained in greater detail below, in response to detecting a fault condition, the fault circuit 42 generates an activation signal 48 that is applied to the gate G of the switch Q 1 , thereby activating the switch Q 1 . Once the switch Q 1 is activated, a short circuit condition may be created within the rectifier 26 . Specifically, the switch Q 1 may create a short circuit at the inputs 44 of the rectifier 26 in response to receiving the activation signal 48 from the fault circuit 42 .

In the non-limiting embodiment as shown in FIG. 1 , the switch Q 1 is a silicon controlled rectifier (SCR), which is also referred to as a thyristor. However, it is to be understood that the switch Q 1 is not limited to an SCR, and that other types of switching elements activated by the fault circuit 42 may be used as well. For example, in the embodiment as shown in FIGS. 3A-3B , the switch Q 1 is a metal oxide semiconductor field-effect transistor (MOSFET). Referring back to FIGS. 2A-2B , those of ordinary skill in the art will appreciate that once activated, the SCR Q 1 may remain activated until current flowing through the SCR Q 1 drops below a respective holding current of the SCR Q 1 . In one non-limiting embodiment, the holding current of the SCR Q 1 is about 2 mA.

Referring to FIGS. 1-2B , the charge pump circuit 32 provides substantially constant DC current to the over voltage circuit 34 , the temperature circuit 36 , and the over current circuit 38 of the fault circuit 42 . In the embodiment as shown in FIGS. 2A-2B , the charge pump circuit 32 may include capacitors C 3 and C 4 , a diode D 7 and a zener diode D 8 . The capacitor C 3 may be used to limit current to the zener diode D 8 . The zener diode D 8 may be used to regulate voltage provided by the charge pump circuit 32 . For example, in one approach the zener diode D 8 may be used to limit the voltage provided to the fault circuit 42 to about 6.2 Volts. The diode D 7 provides rectification and maintains a charge on capacitor C 4 . The diode D 7 also blocks current flow from discharging the capacitor C 4 if the voltage across the zener diode D 8 drops below a power supply voltage V CC of the circuit 10 . In one embodiment, power supply voltage V CC is about 5.6 Volts, however it is to be understood that this voltage is merely exemplary in nature.

The reference voltage circuit 41 includes two resistors R 2 and R 3 that form a voltage divider and a capacitor C 5 . The reference voltage circuit 41 generates a reference voltage V ref which is used by the fault circuit 42 as a reference value in order to detect the fault condition. The fault condition may be at least one of the following: an over voltage condition, an over temperature condition, or an over current condition of the driver circuit 10 . In one exemplary embodiment the over voltage condition is triggered if a bus voltage B+ of the driver circuit 10 exceeds 400 Volts, the over temperature condition is triggered if a temperature of a driver board of the driver circuit 10 (not illustrated) exceeds 110° C., and the over current condition is triggered if current flowing out of the load 18 exceeds 350 mA.

The over voltage circuit 34 of the fault circuit 42 includes a voltage sensing circuit 50 , a comparator U 1 A, a resistor R 9 electrically connected to the power supply voltage V CC , and a diode D 9 . The voltage sensing circuit 50 may include a capacitor C 7 as well as resistors R 5 , R 6 , and R 7 . The resistors R 6 and R 7 create a voltage divider circuit. The bus voltage +B of the driver circuit 10 may flow from the rectifier 26 , through the voltage sensing circuit 50 , and is received by a positive input of the comparator U 1 A.

The reference voltage V ref generated by the reference voltage circuit 41 is received by a negative input of the comparator U 1 A. An output 58 of the comparator U 1 A goes high and generates the activation signal 48 in response to the bus voltage +B exceeding the reference voltage V ref . The output 58 of the comparator U 1 A is electrically connected to the gate G of the switch Q 1 . The activation signal 48 turns the switch Q 1 on, thereby creating a short circuit condition within the rectifier 26 .

Continuing to refer to FIGS. 2A-2B , the over temperature circuit 36 includes a temperature sensing circuit 60 , a comparator U 1 B, a resistor R 10 electrically connected to the power supply voltage V CC , and diode D 10 . The temperature sensing circuit 60 may include a capacitor C 8 as well as a resistor R 8 and a temperature sensing resistor PTC 1 . The resistor R 8 and the temperature sensing resistor PTC 1 create a voltage divider. In the embodiment as shown, the temperature sensing resistor PTC 1 is a positive temperature coefficient resistor (PTC) resistor. The temperature sensing resistor PTC 1 may be used to detect the temperature of the driver board (not illustrated) of the driver circuit 10 .

As the temperature of the driver board increases, the resistance of the temperature sensing resistor PTC 1 increases accordingly, thereby increasing voltage across the temperature sensing resistor PTC 1 . The voltage across the temperature sensing resistor PTC 1 is received by a positive input of the comparator U 1 B. The reference voltage V ref generated by the reference voltage circuit 41 is received by a negative input of the comparator U 1 B. An output 58 of the comparator U 1 B goes high and generates the activation signal 48 in response to the voltage across the temperature sensing resistor PTC 1 exceeding the reference voltage V ref . The output 68 of the comparator U 1 B is electrically connected to the gate G of the switch Q 1 . The activation signal 48 turns the switch Q 1 on, thereby creating a short circuit condition within the rectifier 26 .

The over current circuit 38 includes a current sensing circuit 70 , a comparator U 1 C, a resistor R 11 electrically connected to the power supply voltage V CC , and diode D 11 . The current sensing circuit 70 may include a capacitor C 9 as well as resistors R 4 , R 14 , and R 15 . The current sensing circuit 70 may detect current flowing out of the load 18 ( FIG. 1 ). Specifically, in the embodiment as shown in FIGS. 2A-2B , the load 18 is one or more LEDs (not illustrated). Current flowing from one of the outputs 74 of the driver circuit 10 may flow through the resistors R 4 , R 14 , and R 15 , and is developed into an over current voltage that is received by a positive input of the comparator U 1 C. The over current voltage is indicative of the current flowing from the output 74 of the driver circuit 10 (i.e., the over current voltage is based on current flowing out of the LEDs). The reference voltage V ref generated by the reference voltage circuit 41 is received by a negative input of the comparator U 1 C. An output 78 of the comparator U 1 C goes high and generates the activation signal 48 in response to the over current voltage exceeding the reference voltage V ref . The output 78 of the comparator U 1 C is electrically connected to the gate G of the switch Q 1 . The activation signal 48 turns the switch Q 1 on, thereby creating a short circuit condition within the rectifier 26 .

In the embodiment as shown in FIGS. 2A-2B , the over voltage circuit 34 , the temperature circuit 36 and the over current circuit 38 each include comparators U 1 A, U 1 B, and U 1 C for providing fault protection. However, those of ordinary skill in the art will appreciate that other types of circuitry, such as transistors, may be used instead. Moreover, a resistor R 12 and a capacitor C 13 may be electrically connected to the output 58 , 68 , and 78 of each respective comparator U 1 A, U 1 B, and U 1 C. The resistor R 12 creates a voltage divider circuit with resistors R 9 , R 10 , and R 11 . The capacitor C 13 is a filter capacitor.

FIGS. 3A-3B are an alternative embodiment of a driver circuit 100 . The driver circuit 100 shown in FIGS. 3A-3B are substantially similar to the driver circuit 10 illustrated in FIGS. 2A-2B , except that the switch Q 1 has been replaced with a MOSFET, the fault circuit 42 now includes a latching circuit 102 , and the current sensing circuit 70 includes an extra resistor R 16 located at the output 74 of the driver circuit 100 . In the non-limiting embodiment as shown, the MOSFET is an n-channel MOSFET. Those of ordinary skill in the art will appreciate that a MOSFET may result in lower cost when compared to an SCR.

The latching circuit 102 may be used to hold the fault condition detected by the over voltage circuit 34 , the temperature circuit 36 , or the over current circuit 38 . In the embodiment as shown in FIGS. 3A-3B , the latching circuit 102 includes a resistor R 12 , a capacitor C 14 , a diode D 12 , and a comparator U 1 D. The activation signal 48 generated by the over voltage circuit 34 , the temperature circuit 36 , or the over current circuit 38 is sent to a positive input of the comparator U 1 D. The reference voltage V ref generated by the reference voltage circuit 41 is received by a negative input of the comparator U 1 D. When the activation signal 48 is created (i.e., the fault condition is detected), then the voltage at the positive input of the comparator U 1 D exceeds the reference voltage V ref . Accordingly, an output 108 of the comparator U 1 D goes high (i.e., the activation signal 48 is present at the output 108 of the comparator U 1 D). The output 108 of the comparator U 1 D is electrically connected to the gate G of the switch Q 1 . The activation signal 48 turns the switch Q 1 on, thereby creating a short circuit condition within the rectifier 26 .

FIGS. 4A-4B are yet another embodiment of a driver circuit 200 . The driver circuit 200 shown in FIGS. 4A-4B are substantially similar to the driver circuit 100 shown in FIGS. 3A-3B , except that the switch Q 1 is an SCR, thereby resulting in fewer electrical components included within the driver circuit 200 . Specifically, referring to FIGS. 3A, 3B, 4A and 4B , the driver circuit 200 does not include a diode electrically connected to the outputs of comparators U 1 A, U 1 B, and U 1 C (i.e., diodes D 9 , D 10 , and D 11 ). The driver circuit 200 also does not include a capacitor electrically connected to the outputs of comparators U 1 A, U 1 B, and U 1 C (i.e., capacitors C 11 , C 10 , and C 12 ). The driver circuit 200 also includes only a single resistor R 9 electrically connected to the outputs of comparators U 1 A, U 1 B, and U 1 C (resistors R 10 and R 11 have been omitted from the driver circuit 200 ). Moreover, the resistor R 16 of the current sensing circuit 70 has been omitted in the driver circuit 200 . The latching circuit 102 of the driver circuit 200 also does not include a resistor 12 or the diode D 12 .

Those of ordinary skill in the art will appreciate that although MOSFETs usually result in lower cost, utilizing an SCR for the switch Q 1 may result in fewer components, which in turn may result in decreased complexity and lower overall costs. Furthermore, those of ordinary skill in the art will also appreciate that a non-sensitive gate SCR may be used within the driver circuit 200 as well in order to reduce component costs.

The disclosed circuit 10 as illustrated in FIGS. 1-4B and described above provides a relatively low-cost, precise approach for driving LED lighting, and also eliminates the need for removing the fluorescent ballast in the event a fluorescent tube light is replaced by solid state lighting, such as an LED tube light. Specifically, the high frequency rectification and fault protection provided by the disclosed circuit 10 eliminates the need to remove the fluorescent ballast and provide a replacement driver.

While the forms of apparatus and methods herein described constitute preferred embodiments of this invention, it is to be understood that the invention is not limited to these precise forms of apparatus and methods, and the changes may be made therein without departing from the scope of the invention.