Voltage measuring device

The present invention relates to a voltage measuring device for measuring a voltage across a battery assembly having a plurality of series-connected battery modules each of which is made up of at least one cell.

There have been developed voltage measuring devices for measuring a voltage across a battery assembly having a plurality of series-connected cells or battery modules. See, Japanese Laid-Open Patent Publication No. 2005-003618 (hereinafter referred to as “JP2005-003618A”), Japanese Laid-Open Patent Publication No. 2007-240299 (hereinafter referred to as “JP2007-240299A”), and U.S. Patent Application Publication No. 2008/0203976 (hereinafter referred to as “US2008/0203976A1”).

The object of JP2005-003618A is to provide a power supply voltage measuring device for measuring accurate output voltages by correcting crosstalk (mutual voltage interference) between cells, which occurs in output voltages measured across respective cells due to an additional component that is shared by the cells (paragraph [0005], Abstract).

To achieve the above object, according to JP2005-003618A, opposite ends of a battery 2, which is made up of a plurality of cells 2a through 2e, and junctions between the cells 2a through 2e are connected to respective resistors 5a through 5f, which are connected in pairs through respective capacitors 6a through 6e. The output voltages across the respective cells 2a through 2e are measured through filters that share, among the cells 2a through 2e, the resistors connected to the junctions between the cells 2a through 2e. The power supply voltage measuring device includes a voltage detecting means, having photoMOS relays 7a through 7f and a voltage measuring circuit 8 for detecting voltages across the capacitors 6a through 6e corresponding respectively to the cells 2a through 2e, and a high voltage measuring CPU 1. Based on changes per unit time in the voltages across the capacitors 6a through 6e, the high voltage measuring CPU 1 calculates output voltages across the respective cells 2a through 2e before the voltages across the capacitors 6a through 6e change (Abstract). The power supply voltage measuring device is premised on the fact that the resistors 5a through 5f have identical resistance values, and the capacitors 6a through 6e have identical capacitance values (paragraph [0019]).

According to JP2007-240299A, a task is performed to provide a voltage measuring device, which is capable of increasing noise resistance thereof without delaying the measurement time (paragraph [0022], Abstract). To accomplish this task, according to JP2007-240299A, the resistance of one Rf1 of a pair of resistors Rf1, Rf2, which are connected to the first and (N+1)th voltage detecting terminals of (N+1) voltage detecting terminals, is set to a value smaller than the resistance value of the other resistor Rf2, and the total resistance value of the pair of resistors is set to an equal value in all of a plurality of filters (claim 1, Abstract). The resistances of the resistors Rf1, Rf2 are set to the relationships, Rf1+Rf2=2Rf and Rf1<<Rf2, e.g., Rf=10 kΩ, Rf1=1 kΩ, Rf2=19 kΩ. An electrostatic capacitance of a capacitor Cf, which cooperates with the resistors Rf1, Rf2 to make up an RC filter, is set to 4.7 μF (paragraph [0036]).

US2008/0203976A1 shows an arrangement in which an RC filter is used, which is made up of a plurality of resistors and a capacitor for each of cells BT1 through BT12 (FIG. 1). The patent does not refer to the resistance values of the resistors or the electrostatic capacitance of the capacitor.

As described above, the voltage measuring device disclosed in JP2005-003618A includes so-called RC filters, which are made up of the resistors 5a through 5f and the capacitors 6a through 6e. The voltage measuring device is premised on the fact that the resistors 5a through 5f have identical resistance values, and the capacitors 6a through 6e have identical capacitance values. Therefore, the RC filters disclosed in JP2005-003618A have different filter frequency characteristics for respective measurement channels. The voltage detecting devices disclosed in JP2007-240299A and US2008/0203976A1 also have different filter frequency characteristics for respective measurement channels. Furthermore, according to each of the above documents, since the capacitors must all be connected in series, the layout of the capacitors is limited, thus lowering the degree of design freedom.

In order to equalize the filter frequency characteristics for the respective measurement channels, a voltage measuring device 500 B, as shown in FIG. 10 of the accompanying drawings, for example, may possibly be provided. The voltage measuring device 500 B, which will be described later as a second comparative example, has RC filters, which are made up of resistors 30 a through 30 j (hereinafter collectively referred to as “resistors 30 ”) and capacitors 32 a through 32 j (hereinafter collectively referred to as “capacitors 32 ”). The RC filters are provided independently in association with respective battery modules 16 a through 16 j . The resistors 30 have respective equal resistance values of 100Ω, and the capacitors 32 have respective equal capacitance values of 1 μF.

With the arrangement shown in FIG. 10 , the voltage applied to each of the capacitors 32 becomes greater as the number of series-connected battery modules 16 increases. Further, in the example shown in FIG. 10 , a highest voltage is applied to the capacitor 32 j . Consequently, the arrangement shown in FIG. 10 requires that the capacitors 32 to which higher voltages are applied are capacitors having higher withstand voltage limits.

The present invention has been made in view of the aforementioned problems. It is an object of the present invention to provide a voltage measuring device, which is capable of increasing the degree of design freedom for the RC filters (low-pass filters), while also lowering withstand voltage limits for the capacitors.

According to the present invention, there is provided a voltage measuring device for measuring a voltage across a battery assembly having a plurality of series-connected battery modules each of which is made up of at least one cell, comprising a plurality of measurement nodes including at least one reference node, which is maintained at a reference potential and is connected to one of the battery modules without being connected thereto through a resistor, and non-reference nodes other than the reference node, a plurality of voltage detector sections connected between adjacent ones of the measurement nodes in terms of potential magnitudes, a plurality of resistors having respective ends connected to the non-reference nodes and respective other ends connected to junctions between the battery modules or to opposite ends of the battery assembly, at least one dividing capacitor group having a plurality of dividing capacitors connected in series through the measurement nodes, and having an end connected to the reference node and another end connected to one of the non-reference nodes, and at least one non-dividing capacitor having an end connected to the reference node and another end connected to one of the non-reference nodes to which the dividing capacitors are not connected.

According to the present invention, it is possible to increase the degree of freedom with which the RC filters (low-pass filters) are designed, while at the same time lowering withstand voltage limits for the capacitors.

More specifically, according to the present invention, the voltage measuring device includes a dividing capacitor group having a plurality of dividing capacitors, which are connected in series through measurement nodes. Thus, compared with an arrangement in which all of the capacitors are non-dividing capacitors, it is possible to reduce withstand voltage limits for the dividing capacitors that make up the dividing capacitor group.

Furthermore, according to the present invention, the capacitors included in the RC filters associated with respective battery modules can independently be placed as non-dividing capacitors, or as dividing capacitors which are included in the dividing capacitor group. Consequently, it is possible to increase the degree of freedom with which the capacitors can be placed, compared with an arrangement in which all of the capacitors are placed in series, i.e., an arrangement having only one dividing capacitor group free of non-dividing capacitors.

If it is assumed that product of the electrostatic capacitance of the non-dividing capacitor and a resistance value of one of the resistors, which is connected to the non-dividing capacitor to make up a low-pass filter, serves as a predetermined time constant τ, with respect to the at least one dividing capacitor group, number of the dividing capacitors is represented by n, an integer ranging from 2 to n−1 is represented by m, an integer ranging from 1 to n is represented by q, number of the dividing capacitors from the reference node to one of the dividing capacitors in question is represented by k q , number of the non-reference nodes from the reference node to one of the non-reference nodes, which is connected to a terminal of a k q th one of the dividing capacitors remote from the reference node, is represented by L kq , electrostatic capacitance of the k q th one of the dividing capacitors is represented by C kq , and a resistance value of one of the resistors, which is connected to the k q th one of the dividing capacitors, is represented by R kq , then the electrostatic capacitance C kq of each of the dividing capacitors satisfies the following inequalities (1) and (2), and the resistance value R kq of each of the resistors satisfies the following equations (3) through (5):

Consequently, it is possible to make the frequency characteristics of the RC filters uniform. More specifically, with respect to the non-dividing capacitors and the resistors, which are paired with the non-dividing capacitors to make up the RC filters, the product of the electrostatic capacitances of the non-dividing capacitors and the resistance values of the resistors serves as a time constant τ. Since the electrostatic capacitances of the dividing capacitors satisfy inequalities (1) and (2) and the resistance values of the resistors, which are paired with the dividing capacitors to make up the RC filters, satisfy equations (3) through (5), the time constant τ of each of the RC filters is constant. Consequently, the RC filters including any of the non-dividing capacitors and the dividing capacitors have uniform filter frequency characteristics (filter time constants).

The electrostatic capacitances C kq of the dividing capacitors also satisfy inequalities (1) and (2). Therefore, taking into account the term “(L k2 −L k1 )/L k1 ” in inequality (1) and the term “(L k(m+1) −L km )/(L km −L k(m−1) )” in inequality (2), it is possible to give the electrostatic capacitances of the dividing capacitors a relative degree of freedom, and to use inexpensive general-purpose capacitors as the dividing capacitors. For example, it is possible to equalize the electrostatic capacitances of the dividing capacitors by setting “(L k2 −L k1 )/L k1 ” in inequality (1) and “(L k(m+1) −L km )/(L km −L k(m−1) )” in inequality (2) to numerical values greater than 0 and less than or equal to 1.

On the other hand, compared with the choices available for the electrostatic capacitances of general-purpose capacitors, the choices available for the resistance values of general-purpose resistors are greater. Trimmer resistors, the resistance values of which are adjustable as desired, are also generally available. In addition, it is easy to adjust the resistance values by combining series-connected resistors and parallel-connected resistors. Consequently, it is easier to satisfy equations (3) through (5) for the resistors than to select the capacitors, thereby making it possible to minimize the cost of the voltage measuring device.

According to the present invention, there also is provided a voltage measuring device for measuring a voltage across a battery assembly having a module array made up of a plurality of series-connected battery modules each of which is made up of at least one cell, comprising a voltage detecting unit for detecting voltages across the battery modules, the voltage detecting unit being connected to positive and negative pole sides of the battery modules through at least as many lines as number of the battery modules +1, the lines being connected to junctions between the battery modules and opposite ends of the module array, as many resistors as the number of the battery modules, the resistors being connected to as many lines as the number of the battery modules, among the at least as many lines as the number of the battery modules +1, and as many capacitors as the number of the battery modules, which are combined with the resistors to make up RC filters, wherein the capacitors include at least one first capacitor connected in series to other capacitors, and a plurality of second capacitors connected in series to other capacitors, the second capacitors being combined into at least one series-connected capacitor group, the first capacitor has an end connected through one of the lines to a particular pole side as a positive or negative pole side of the battery modules, the first capacitor has another end connected to a reference line as one of the lines, which is free of any of the resistors, the second capacitors have ends connected to particular pole sides or to opposite sides of the battery modules through certain ones of the lines, and one of the second capacitors, which is closest to the reference line, of the at least one series-connected capacitor group has another end connected to the reference line, and the others of the second capacitors have other ends, which are connected to the ends of the second capacitors on non-reference lines that serve as other lines apart from the reference line.

According to the present invention, it is possible to increase the degree of freedom with which the RC filters (low-pass filters) are designed, while at the same time lowering withstand voltage limits for the capacitors.

More specifically, according to the present invention, the voltage measuring device includes a series-connected capacitor group having a plurality of series-connected capacitors (second capacitors). Thus, it is possible to reduce the withstand voltage limits for the capacitors (second capacitors) that make up the series-connected capacitor group, compared with an arrangement in which all of the capacitors are capacitors (first capacitors), which are not connected in series to other capacitors.

Furthermore, according to the present invention, the capacitors included in the RC filters associated with respective battery modules can independently be placed as first capacitors, which are not connected in series to other capacitors, or as second capacitors, which are included in the series-connected capacitor group. Consequently, it is possible to increase the degree of freedom with which the capacitors can be placed, compared with an arrangement in which all of the capacitors are placed in series, i.e., an arrangement having only one series-connected capacitor group free of first capacitors.

If it is assumed that each of the RC filters has a time constant represented by a particular value τ, product of the electrostatic capacitance of the first capacitor and a resistance value of one of the resistors, which is paired with the first capacitor, is represented by τ, with respect to the one series-connected capacitor group, number of the second capacitors is represented by n, an integer ranging from 2 to n−1 is represented by m, an integer ranging from 1 to n is represented by q, number of the second capacitors from the reference line to one of the second capacitors in question is represented by k q , number of the non-reference lines from the reference line to one of the non-reference lines, which is connected to a terminal of a k q th one of the second capacitors remote from the reference line, is represented by L kq , electrostatic capacitance of the k q th one of the second capacitors is represented by C kq , and a resistance value of one of the resistors, which is connected to the k q th one of the second capacitors, is represented by R kq , then the electrostatic capacitance C kq of each of the second capacitors satisfies the following inequalities (6) and (7), and the resistance value R kq of each of the resistors satisfies the following equations (8) through (10):

Consequently, it is possible to make the frequency characteristics of the RC filters uniform. More specifically, with respect to the first capacitors and the resistors, which are paired with the first capacitors to make up the RC filters, the product of the electrostatic capacitances of the first capacitors and the resistance values of the resistors serves as a time constant τ. Since the electrostatic capacitances of the second capacitors satisfy inequalities (6) and (7) and the resistance values of the resistors, which are paired with the second capacitors to make up the RC filters, satisfy equations (8) through (10), the time constant τ of each of the RC filters is constant. Consequently, the RC filters including any of the first capacitors and the second capacitors have uniform filter frequency characteristics (filter time constants).

The electrostatic capacitances C kq of the second capacitors may also satisfy inequalities (6) and (7). Therefore, taking into account the term “(L k2 −L k1 )/L k1 ” in inequality (6) and the term “(L k(m+1) −L km )/(L km −L k(m−1) )” in inequality (7), it is possible to give the electrostatic capacitances of the second capacitors a relative degree of freedom, and to use inexpensive general-purpose capacitors as the second capacitors. For example, it is possible to equalize the electrostatic capacitances of the second capacitors by setting “(L k2 −L k1 )/L k1 ” in inequality (6) and “(L k(m+1) −L km )/(L km −L k(m−1) )” in inequality (7) to a numerical value greater than 0 and less than or equal to 1.

On the other hand, compared with the choices available for the electrostatic capacitances of general-purpose capacitors, the choices available for the resistance values of general-purpose resistors are greater. Trimmer resistors, the resistance values of which are adjustable as desired, are also generally available. In addition, it is easy to adjust the resistance values by combining series-connected resistors and parallel-connected resistors. Consequently, it is easier to satisfy equations (8) through (10) by selecting the resistors than by selecting the capacitors, thereby making it possible to minimize the cost of the voltage measuring device.

FIG. 1 is a circuit diagram showing an overall arrangement of a voltage measuring device according to a first embodiment of the present invention;

FIG. 2 is a circuit diagram showing a portion of a first voltage measuring device, which is used to illustrate an arrangement of the voltage measuring device according to the first embodiment;

FIG. 3 is a circuit diagram showing a portion of a second voltage measuring device, which is used to illustrate an arrangement of the voltage measuring device according to the first embodiment;

FIG. 4 is a circuit diagram showing a portion of a third voltage measuring device, which is used to illustrate an arrangement of the voltage measuring device according to the first embodiment;

FIG. 5 is a circuit diagram showing a portion of an example of the voltage measuring device according to the first embodiment;

FIG. 6 is a diagram showing a specific example (first inventive example) of numerical values of resistors and capacitors in the arrangement of the voltage measuring device shown in FIG. 1 ;

FIG. 7 is a diagram showing by way of example frequency characteristics of RC filters, which were plotted during use of the voltage measuring device shown in FIG. 6 ;

FIG. 8 is a diagram showing a specific example of numerical values of resistors and capacitors in the arrangement of a voltage measuring device according to a first comparative example;

FIG. 9 is a diagram showing by way of example frequency characteristics of RC filters, which were plotted during use of the voltage measuring device shown in FIG. 8 ;

FIG. 10 is a diagram showing a specific example of numerical values of resistors and capacitors in the arrangement of a voltage measuring device according to a second comparative example;

FIG. 11 is a diagram showing by way of example frequency characteristics of RC filters, which were plotted during use of the voltage measuring device shown in FIG. 10 ;

FIG. 12 is a circuit diagram showing a portion of a voltage measuring device according to a second embodiment of the present invention;

FIG. 13 is a circuit diagram showing a portion of a first voltage measuring device, which is used to illustrate an arrangement of the voltage measuring device according to the second embodiment;

FIG. 14 is a circuit diagram showing a portion of a second voltage measuring device, which is used to illustrate an arrangement of the voltage measuring device according to the second embodiment;

FIG. 15 is a circuit diagram showing a portion of a third voltage measuring device, which is used to illustrate an arrangement of the voltage measuring device according to the second embodiment;

FIG. 16 is a circuit diagram showing a portion of an example of the voltage measuring device according to the second embodiment;

FIG. 17 is a diagram showing a specific example (second inventive example) of numerical values of resistors and capacitors in the arrangement of the voltage measuring device shown in FIG. 12 ;

FIG. 18 is a diagram showing a specific example (third inventive example) of numerical values of resistors and capacitors in an arrangement (modification of FIG. 12 ) including plural combinations of three RC filters;

FIG. 19 is a circuit diagram showing a portion of a voltage measuring device according to a third embodiment of the present invention;

FIG. 20 is a diagram showing a specific example (fourth inventive example) of numerical values of resistors and capacitors in the arrangement of the voltage measuring device shown in FIG. 19 ;

FIG. 21 is a diagram showing a specific example (fifth inventive example) of numerical values of resistors and capacitors in an arrangement (modification of FIG. 19 ), which makes use of a positive-most pole line of a module array as a reference line, and which has three dividing capacitor groups (series-connected capacitor groups);

FIG. 22 is a diagram showing a specific example (sixth inventive example) of numerical values of resistors and capacitors in an arrangement (modification of FIG. 19 ), which makes use of a central line of a module array as a reference line, and which has four dividing capacitor groups (series-connected capacitor groups); and

FIG. 23 is a diagram showing a specific example (seventh inventive example) of numerical values of resistors and capacitors in an arrangement (modification of FIG. 19 ), which makes use of positive-most and negative-most pole lines of a module array as reference lines, and which has four dividing capacitor groups (series-connected capacitor groups).

A. First Embodiment (Arrangement in which Two RC Filters are Combined)

A-1. Overall Arrangement

FIG. 1 is a circuit diagram showing an overall arrangement of a voltage measuring device 10 according to a first embodiment of the present invention. The voltage measuring device 10 has an arrangement in which two RC filters are combined. As shown in FIG. 1 , the voltage measuring device 10 includes a battery assembly 12 having a module array 14 made up of a plurality of series-connected battery modules 16 (hereinafter referred to as “modules 16 ”), a voltage measuring circuit 18 to which voltages across the modules 16 (hereinafter referred to as “module voltages Vm”) are applied, and a processor 20 for detecting module voltages Vm based on an output signal from the voltage measuring circuit 18 . The voltage measuring circuit 18 and the processor 20 jointly make up a voltage detecting means.

Each of the modules 16 comprises at least one cell. According to the first embodiment, each of the modules 16 includes one cell.

Nodes (segmentation points) between the modules 16 and nodes at opposite ends of the module array 14 serve as cell nodes 22 . Between the cell nodes 22 and a positive input terminal 26 and a negative input terminal 28 of the voltage measuring circuit 18 , as many lines 24 as the number of modules 16 (hereinafter referred to as a “module number”) plus 1 are provided, thereby connecting positive and negative pole sides of the modules 16 to the positive input terminal 26 or the negative input terminal 28 of the voltage measuring circuit 18 .

More specifically, the positive pole side of a certain module 16 , for example, the module 16 on the negative-most pole side (lowermost in FIG. 1 ) of the module array 14 (hereinafter referred to as a “lowermost module 16 ”), is connected to the positive input terminal 26 of the voltage measuring circuit 18 , whereas the negative pole side of the lowermost module 16 is connected to the negative input terminal 28 of the voltage measuring circuit 18 . The positive pole side of a module 16 adjacent to the lowermost module 16 (i.e., a module 16 at a next level up from the lowermost module 16 ) is connected to the negative input terminal 28 of the voltage measuring circuit 18 , whereas the negative pole side of the same module 16 is connected to the positive input terminal 26 of the voltage measuring circuit 18 .

Among all of the lines 24 , the lines 24 (hereinafter referred to as “non-reference lines 24 n ”) except for one line 24 (hereinafter referred to as a “reference line 24 ref”) include respective resistors 30 . There are as many capacitors 32 as the number of modules 16 , and the capacitors 32 are paired with respective resistors 30 to make up RC filters. The capacitors 32 include capacitors 32 (hereinafter referred to as “non-dividing capacitors 32 nd ” or “first capacitors 32 nd ”), which are not connected in series to other capacitors 32 , and capacitors 32 (hereinafter referred to as “dividing capacitors 32 div” or “second capacitors 23 div”), which are connected in series to the other capacitors 32 . The combination of the series-connected dividing capacitors 32 div will be referred to as a “dividing capacitor group 36 ” or a “series-connected capacitor group 36 ”.

Respective ends of the non-dividing capacitors 32 nd are connected to positive pole sides of the respective modules 16 by the non-reference lines 24 n , and respective other ends thereof are connected to the reference line 24 ref, which is free of a resistor 30 . To each of the non-dividing capacitors 32 nd , there is applied the sum of the module voltages VM of the modules 16 up to the module 16 to which one end of the non-dividing capacitor 32 nd is connected.

For example, one end of the second lowermost capacitor 32 (electrostatic capacitance C 102 ) in FIG. 1 is connected to the positive pole side of the second lowermost module 16 in FIG. 1 . Therefore, the voltage applied across the capacitor 32 (electrostatic capacitance C 102 ) is represented by the sum (V 1 +V 2 ) of the module voltages Vm of the lowermost and second lowermost modules 16 . Similarly, one end of the third lowermost capacitor 32 (electrostatic capacitance C 103 ) in FIG. 1 is connected to the positive pole side of the third lowermost module 16 in FIG. 1 . Therefore, the voltage applied across the capacitor 32 (electrostatic capacitance C 103 ) is represented by the sum (V 1 +V 2 +V 3 ) of the module voltages Vm of the lowermost through third lowermost modules 16 .

Respective ends of the dividing capacitors 32 div (positive pole side ends in FIG. 1 ) are connected to positive pole sides of the respective modules 16 by the non-reference lines 24 n . Among the dividing capacitors 32 div, the dividing capacitor 32 div that is closest to the reference line 24 ref (the capacitor 32 having an electrostatic capacitance C 10s in FIG. 1 ) has another end (negative pole side end in FIG. 1 ), which is connected to the reference line 24 ref. Among the dividing capacitors 32 div, the dividing capacitor 32 other than the dividing capacitor 32 div that is closest to the reference line 24 ref (the capacitor 32 having an electrostatic capacitance C 10p in FIG. 1 ) has another end, which is connected on the non-reference line 24 n to the end of the other dividing capacitor 32 div (the capacitor 32 having the electrostatic capacitance C 10s ) belonging to the same dividing capacitor group 36 .

The sum of the module voltages Vm of the modules 16 up to the module 16 to which one end of the dividing capacitor 32 div is connected is not applied to each of the dividing capacitors 32 div. Rather, a portion of the sum of such module voltages Vm is applied thereto. Stated otherwise, the voltage applied across each of the dividing capacitors 32 div is represented by a voltage that is divided by the other dividing capacitor 32 div.

The lines 24 include respective switches 38 , which are positioned closer to the voltage measuring circuit 18 than the capacitors 32 (the non-dividing capacitors 32 nd and the dividing capacitors 32 div). Each of the switches 38 comprises a semiconductor switch, for example, which is turned on and off depending on a control signal supplied thereto from a control circuit 40 .

The control circuit 40 turns the switches 38 on and off in sequence, so as to connect the modules 16 sequentially to the voltage measuring circuit 18 . For example, for connecting the lowermost module 16 and the voltage measuring circuit 18 , the control circuit 40 turns on the two switches 38 on the two lines 24 that interconnect the lowermost module 16 and the voltage measuring circuit 18 , and turns off the other switches 38 . When turned on, the switches 38 provide measurement channels CH (voltage detecting sections) interconnecting the modules 16 and the voltage measuring circuit 18 , whereupon the voltage measuring circuit 18 generates output signals representing module voltages Vm of the respective modules 16 . There are as many measurement channels CH as the number of modules 16 (module number).

The battery assembly 12 according to the present embodiment may be either a primary battery or a secondary battery. A suitable primary battery includes a fuel battery, and a suitable secondary battery includes a lithium ion battery, a nickel hydrogen battery, and a capacitor.

The voltage measuring device 10 can measure the module voltages Vm according to the process disclosed in JP2005-003618A, for example.

For illustrative purposes, the resistance value of each of the resistors 30 is denoted by R 10x in FIG. 1 , where the subscript “x” represents an integer in a range from 1 to p, and which indicates the location counted from the reference line 24 ref. For example, the resistance value of the resistor 30 on the first non-reference line 24 n from the reference line 24 ref is denoted by R 101 . In this case, “p” is equal to the module number. Therefore, the total number of modules 16 (module number) and the total number of resistors 30 are represented by p.

Similarly, for illustrative purposes, the electrostatic capacitance of each of the capacitors 32 is denoted by C 10x in FIG. 1 , where the subscript “x” indicates the location counted from the reference line 24 ref, as described above. For example, the electrostatic capacitance of the first capacitor 32 from the reference line 24 ref is denoted by C 101 , and the electrostatic capacitance of the second capacitor 32 from the reference line 24 ref is denoted by C 102 . The total number of capacitors 32 is the same as the module number p.

Nodes on opposite ends of each of the capacitors 32 are referred to as “measurement nodes 44 ”. The measurement nodes 44 are nodes (segmentation points) connected to the voltage measuring circuit 18 . Two adjacent measurement nodes 44 jointly form a measurement channel CH corresponding to a single module 16 and which is connected to the voltage measuring circuit 18 . Measurement nodes 44 that are positioned on the reference line 24 ref are referred to as reference nodes 44 ref, whereas measurement nodes 44 that are positioned on the non-reference lines 24 n are referred to as non-reference nodes 44 n . The term “s” represents any integer that satisfies the inequality 3<s−1<s<p−1<p.

A-2. Basic Concept of Resistance Value R 10n and Electrostatic Capacitance C 10n

A-2-1. General Principles

A process of establishing the resistance value R 10n of a resistor 30 and the electrostatic capacitance C 10n of a capacitor 32 will be described below. According to the first embodiment in which two RC filters are combined, the resistance value R 10n and the electrostatic capacitance C 10n are established in the following manner.

With respect to the non-dividing capacitors 32 nd , the resistance value R 10n and the electrostatic capacitance C 10n thereof are established such that the time constant of each RC filter will be of a characteristic value τ. Stated otherwise, the resistance value R 10n and the electrostatic capacitance C 10n can be set to any values, insofar as the product of the resistance value R 10n and the electrostatic capacitance C 10n is represented by τ.

With respect to the dividing capacitors 32 div, the following definitions are given initially.

n: the number of dividing capacitors 32 div

q: an integer in a range from 1 to n

k q : the number of dividing capacitors 32 div from the reference line 24 ref to a dividing capacitor 32 div in question (including a dividing capacitor 32 div in question)

L kq : the number of non-reference lines 24 n from the reference line 24 ref to a non-reference line 24 n that is connected to the terminal of the k q th dividing capacitor 32 div remote from the reference line 24 ref (the positive pole side terminal of the dividing capacitor 32 div in FIG. 1 )

C kq : the electrostatic capacitance of the k q th dividing capacitor 32 div

R kq : the resistance value of the resistor 30 that is connected to the k q th dividing capacitor 32 div

In FIG. 1 , k 1 corresponds to the capacitor 32 having an electrostatic capacitance C 10s , and k 2 corresponds to the capacitor 32 having an electrostatic capacitance C. The number L k1 corresponding to the capacitor 32 having the electrostatic capacitance C 10s is represented by “s”, and the number L k2 corresponding to the capacitor 32 having the electrostatic capacitance C 10p is represented by “p”.

According to the above definitions, the electrostatic capacitance C kq of each of the dividing capacitors 32 div is established to satisfy an inequality (1-1) below, and the resistance R kq of each of the resistors 30 is established to satisfy equations (1-2) and (1-3) below.

A-2-2. Specific Example

A process for introducing the above inequality and equations (1-1) through (1-3) will be described below by way of a specific example. FIGS. 2 through 4 are circuit diagrams showing portions of first through third voltage measuring devices 100 A through 100 C (hereinafter referred to as “voltage measuring devices 100 A through 100 C”), which are used to illustrate arrangements of the voltage measuring device 10 according to the first embodiment. Components thereof, which are identical to the components shown in FIG. 1 , are denoted by identical reference characters.

It should be noted that FIGS. 2 through 4 serve to illustrate arrangements of the voltage measuring device 10 according to the above-described first embodiment, i.e., to introduce the arrangement thereof shown in FIG. 5 , but do not show the arrangement of the voltage measuring device 10 itself. In other words, an exemplary arrangement of the voltage measuring device 10 is shown in FIG. 5 .

The voltage measuring devices 10 and 100 A through 100 C all include the voltage measuring circuit 18 , the processor 20 , the switches 38 , and the controller 40 , etc., as in the case of FIG. 1 , although these components are omitted from illustration in FIGS. 2 through 5 .

The voltage measuring device 100 A shown in FIG. 2 includes a battery assembly 12 having a module array 14 , which is made up of a plurality of (six) series-connected battery modules 16 a through 16 f (hereinafter referred to as “modules 16 a through 16 f ” and collectively referred to as “modules 16 ”), as many resistors 30 a through 30 f (hereinafter collectively referred to as “resistors 30 ”) as the number of modules 16 , and as many capacitors 132 a through 132 f as the number of modules 16 . The capacitors 132 a through 132 f are not connected in series, but have respective ends (positive pole sides) thereof, which are connected by non-reference lines 24 n to positive pole sides of the respective modules 16 , and respective other ends (negative pole sides) thereof, which are connected to a reference line 24 ref that is free of a resistor 30 . The capacitors 132 a through 132 f shown in FIG. 2 correspond to the non-dividing capacitors (first capacitors). Therefore, RC filters made up of the resistors 30 and the capacitors 132 a through 132 f operate independently of each other.

The resistors 30 have respective resistance values R 10x denoted by R 101 through R 106 counted from the reference line 24 ref (upwardly in FIG. 2 ). The capacitors 132 a through 132 f have respective electrostatic capacitances C 11x denoted by C 111 through C 116 .

In FIG. 2 , it is assumed that the RC products (R 10x ·C 11x ) (where x represents an integer in a range from 1 through 6) of the RC filters are equal to each other, and that the voltages across respective modules 16 (module voltages Vm) are uniform. In this case, the RC filters have respective uniform output voltages V 1 , V 2 , V 3 , V 4 , V 5 , and V 6 .

As shown in FIG. 3 , the capacitor 132 f shown in FIG. 2 can be replaced with six series-connected capacitors 132 g having an electrostatic capacitance C 166 , which is six times the electrostatic capacitance C 116 (C 166 =C 116 ×6). Since the voltage across the capacitors 132 g is divided into six equal voltages, as shown in FIG. 3 , the voltage at point B is equal to the voltage at point A.

Therefore, even if one of the midpoints (point B) between the capacitors 132 g (intermediate points between adjacent ones of the capacitors 132 g ) is connected to a corresponding line 24 , as shown in FIG. 4 , the output voltages V 1 through V 6 of the RC filters remain the same as those shown in FIG. 2 .

Furthermore, as shown in FIG. 5 , the group of parallel-connected capacitors shown in FIG. 4 may be replaced with a single capacitor. More specifically, as shown in FIG. 5 , the single capacitor 132 d and the four capacitors 132 g , which are connected between the positive pole side of the module 16 d (points A and B shown in FIG. 4 ) and the line 24 connected to ground, are replaced with a single capacitor 132 h . Even if such a replacement is made, the output voltages V 1 through V 6 of the RC filters remain the same as those shown in FIG. 2 .

Assuming that the capacitors 132 d , 132 g , 132 h have respective electrostatic capacitances C 114 , C 166 , C 104 , then the electrostatic capacitance C 104 is determined by the following equation (2-1), due to the relationships shown in FIGS. 2 through 5 .

If the time constant of each of the RC filters is represented by a particular constant τ, then the relationship according to the following equation (2-2) is satisfied.

As shown in FIG. 5 , the two capacitors 132 g between the lines 24 that are connected to the negative pole side (point B) of the module 16 e and the positive pole side (point C) of the module 16 f shown in FIG. 4 are replaced with a single capacitor 132 i . Assuming that the capacitors 132 f , 132 g , 132 i have respective electrostatic capacitances C 116 , C 166 , C 106 , then the electrostatic capacitance C 106 is determined by the following equation (2-3), due to the relationships shown in FIGS. 2 through 5 .

If the time constant of each of the RC filters is represented by a particular constant τ, then the relationship according to the following equation (2-4) is satisfied.

Based on equation (2-4), the resistance value R 106 of the resistor 30 f can be established according to the following equation (2-5).

The following equation (2-6) can be derived from equation (2-2) and equation (2-5).

Consequently, based on equation (2-6), the resistance value R 104 of the resistor 30 d can be established according to the following equation (2-7).

According to the above-described process, it is possible to establish the electrostatic capacitances C 104 , C 106 of the dividing capacitors 132 h , 132 i and the resistance values R 104 , R 106 of the resistors 30 d , 30 f.

A-3. Specific Inventive Example and First and Second Comparative Examples

FIG. 6 is a diagram showing a specific example (first inventive example) of numerical values for the resistors 30 ( 30 a through 30 j ) and the capacitors 32 ( 32 a through 32 j ) in the arrangement of the voltage measuring device 10 shown in FIG. 1 . FIG. 7 is a diagram showing by way of example frequency characteristics of the RC filters, which were plotted during use of the voltage measuring device shown in FIG. 6 . In FIG. 7 , the vertical axis represents the frequency [Hz] (logarithmic notation) of an input signal supplied to the RC filters, whereas the horizontal axis represents the gain [dB].

FIG. 8 is a diagram showing a specific example of numerical values of the resistors 30 ( 30 a through 30 j ) and the capacitors 32 ( 32 a through 32 j ) in an arrangement of a voltage measuring device 500 A according to a first comparative example. FIG. 9 is a diagram showing by way of example frequency characteristics of RC filters, which were plotted during use of the voltage measuring device 500 A shown in FIG. 8 . FIG. 10 is a diagram showing a specific example of numerical values of the resistors 30 ( 30 a through 30 j ) and the capacitors 32 ( 32 a through 32 j ) in an arrangement of a voltage measuring device 500 B according to a second comparative example. FIG. 11 is a diagram showing by way of example frequency characteristics of RC filters, which were plotted during use of the voltage measuring device 500 B shown in FIG. 10 .

In FIGS. 6, 8, and 10 , the battery modules 16 ( 16 a through 16 j ) are indicated as an AC sign, due to the fact that the battery modules 16 are made up of cells the voltages of which vary as the battery modules 16 are charged and discharged.

The voltage measuring device 500 A according to the first comparative example shown in FIG. 8 has all of the capacitors 32 connected in series, unlike the voltage measuring device 10 according to the first embodiment shown in FIG. 6 . The resistors 30 have identical resistance values R 101 through R 110 each of which is 100Ω, and the capacitors 32 have identical electrostatic capacitances C 101 through C 110 each of which is 1 μF.

As shown in FIG. 9 , frequency characteristics of the RC filters in the respective stages (measurement channels CH) of the voltage measuring device 500 A shown in FIG. 8 differ widely from each other.

In the voltage measuring device 500 B according to the second comparative example shown in FIG. 10 , all of the capacitors 32 are not connected in series, unlike the voltage measuring device 10 according to the first embodiment shown in FIG. 6 . Therefore, the RC filters, which are made up of the resistors 30 and the capacitors 32 , operate independently of each other. The resistors 30 have identical resistance values R 101 through R 110 each of which is 100Ω, and the capacitors 32 have identical electrostatic capacitances C 101 through C 110 each of which is 1 μF.

As shown in FIG. 11 , the frequency characteristics of the RC filters in the respective stages (measurement channels CH) of the voltage measuring device 500 B shown in FIG. 10 are uniform. However, since the voltages applied to certain capacitors 32 (e.g., the capacitors 32 h through 32 j ), which are positioned closer to the positive pole side of the module array 14 (the upper side in FIG. 10 ), are higher, it is necessary to increase the withstand voltage limits for the capacitors 32 that are closer to the positive pole side.

As shown in FIG. 6 , the voltage measuring device 10 according to the first embodiment has the capacitors 32 a through 32 e and 32 g through 32 i , which serve as the non-dividing capacitors 32 nd (first capacitors 32 nd ), and the capacitors 32 f , 32 j , which serve as the dividing capacitors 32 div (second capacitors 32 div), used in combination. Consequently, it is possible to increase the degree of freedom with which the RC filters are designed, while at the same time lowering withstand voltage limits for the capacitors 32 .

The voltage measuring device 10 shown in FIG. 6 is designed according to the following sequence, for example. First, a required time constant τ is established. According to the first inventive example, the time constant τ=100 μsec.

Thereafter, electrostatic capacitances C 10x of the capacitors 32 are determined. According to the first inventive example, the product of the electrostatic capacitances C 101 through C 105 and C 107 through C 109 of the non-dividing capacitors 32 a through 32 e and 32 g through 32 i , and the resistance values R 101 through R 105 and R 107 through R 109 of the resistors 30 a through 30 e and 30 g through 30 i , which are paired with the non-dividing capacitors 32 a through 32 e and 32 g through 32 i , is represented by τ. Therefore, the electrostatic capacitances C 101 through C 105 and C 107 through C 109 of the non-dividing capacitors 32 a through 32 e and 32 g through 32 i can be established comparatively freely.

According to the first inventive example, each of the electrostatic capacitances C 101 through C 105 and C 107 through C 109 of the non-dividing capacitors 32 a through 32 e and 32 g through 32 i is established as 1 μF. Accordingly, each of the resistance values R 101 through R 105 and R 107 through R 109 of the resistors 30 a through 30 e and 30 g through 30 i is established as 100Ω.

The electrostatic capacitances C 106 , C 110 of the dividing capacitors 32 f , 32 j , which satisfy the above inequality (1-1), are established as 2.2 μF each.

The resistance values R 106 , R 110 of the resistors 30 f , 30 j , which are paired with the dividing capacitors 32 f , 32 j , are established as 136Ω and 114Ω (rounded off to whole numbers), respectively, based on equations (1-2) and (1-3) and the electrostatic capacitance C 106 . In the inequality and equations (1-1), (1-2), and (1-3), the numbers L k1 and L k2 (i.e., the numbers of the non-reference lines 24 n from the reference line 24 ref to the non-reference lines 24 n that are connected to the respective terminals of the capacitors 32 g , 32 j , which are located remotely (toward the positive pole side) from the reference line 24 ref), are represented by 6 and 10 , respectively.

With the arrangement shown in FIG. 6 , as shown in FIG. 7 , it is possible to realize a certain time constant τ and to make the frequency characteristics of the RC filters uniform.

A-4. Advantages of the First Embodiment

The first embodiment has an arrangement in which two RC filters are combined together, whereas a third embodiment, to be described later, has an arrangement (a more general arrangement) in which the number of combined RC filters is unlimited. Therefore, the advantages of the first embodiment will be described in detail in connection with the third embodiment.

B. Second Embodiment (Arrangement in which Three RC Filters are Combined)

B-1. Overall Arrangement

FIG. 12 is a circuit diagram showing a portion of a voltage measuring device 10 A according to a second embodiment of the present invention. The voltage measuring device 10 A according to the second embodiment is basically of the same arrangement as the voltage measuring device 10 according to the first embodiment, but differs therefrom in that, while the voltage measuring device 10 according to the first embodiment has two dividing capacitors 32 div combined to provide two RC filters, the voltage measuring device 10 A according to the second embodiment has three dividing capacitors 32 div combined to provide three RC filters.

The voltage measuring device 10 A includes the voltage measuring circuit 18 , the processor 20 , the switches 38 , the controller 40 , etc., similar to the case shown in FIG. 1 , although such components are omitted from illustration in FIG. 12 . In FIG. 12 , the terms “s” and “t” represent integers that satisfy the inequality 3<s−1<s<t−1<t<p−1<p.

B-2. Basic Concept of Resistance Value R 20x and Electrostatic Capacitance C 20x

B-2-1. General Principles

A process of establishing the resistance value R 20x of a resistor 30 and the electrostatic capacitance C 20x of a capacitor 32 in the second embodiment will be described below. According to the second embodiment, in which three RC filters are combined, the resistance value R 20x and the electrostatic capacitance C 20x are established in the following manner.

With respect to a non-dividing capacitor 32 nd , the resistance value R 20x and the electrostatic capacitance C 20x thereof are established such that the time constant of each RC filter will be a characteristic value τ. Stated otherwise, the resistance value R 20x and the electrostatic capacitance C 20x can be set to any values, insofar as the product of the resistance value R 20x and the electrostatic capacitance C 20x is represented by τ.

With respect to a dividing capacitor 32 div, the following definitions are given initially.

n: the number of dividing capacitors 32 div

q: an integer in a range from 1 to n

k q : the number of dividing capacitors 32 div from the reference line 24 ref to a dividing capacitor 32 div in question (including a dividing capacitor 32 div in question)

L kq : the number of non-reference lines 24 n from the reference line 24 ref to a non-reference line 24 n that is connected to the terminal of the k q th dividing capacitor 32 div remote from the reference line 24 ref (the positive pole side terminal of the dividing capacitor 32 div shown in FIG. 12 )

C kq : the electrostatic capacitance of the k q th dividing capacitor 32 div

R kq : the resistance value of the resistor 30 that is connected to the k q th dividing capacitor 32 div

In FIG. 12 , k 1 corresponds to a capacitor 32 having an electrostatic capacitance C 20s , k 2 corresponds to a capacitor 32 having an electrostatic capacitance C 20t , and k 3 corresponds to a capacitor 32 having an electrostatic capacitance C 20p . The number L k1 corresponding to the capacitor 32 having the electrostatic capacitance C 20s is represented by “s”, the number L k2 corresponding to the capacitor 32 having the electrostatic capacitance C 20t is represented by “t”, and the number L k3 corresponding to the capacitor 32 having the electrostatic capacitance C 20p is represented by “p”.

According to the above definitions, the electrostatic capacitance C kq of each of the dividing capacitors 32 div is established to satisfy inequalities (3-1) and (3-2) below, and the resistance R kq of each of the resistors 30 is established to satisfy equations (3-3), (3-4), and (3-5) below.

B-2-2. Specific Example

A process for introducing the above inequalities and equations (3-1) through (3-5) will be described below by way of a specific example. FIGS. 13 through 15 are circuit diagrams showing portions of first through third voltage measuring devices 200 A through 200 C (hereinafter referred to as “voltage measuring devices 200 A through 200 C”), which are used to illustrate arrangements of the voltage measuring device 10 A according to the second embodiment. FIG. 16 is a circuit diagram showing a portion of an example of the voltage measuring device 10 A according to the second embodiment. Components thereof, which are identical to the components according to the first embodiment ( FIG. 1 , etc.) and shown in FIG. 12 , are denoted by identical reference characters.

It should be noted that FIGS. 13 through 15 serve to illustrate arrangements of the voltage measuring device 10 A according to the above-described second embodiment, i.e., to introduce an arrangement thereof shown in FIG. 16 , but do not show the arrangement of the voltage measuring device 10 A itself. In other words, FIG. 16 shows an exemplary arrangement of the voltage measuring device 10 A.

The voltage measuring devices 10 A and 200 A through 200 C all include the voltage measuring circuit 18 , the processor 20 , the switches 38 , and the controller 40 , etc., as in the case of the first embodiment ( FIG. 1 ), although these components are omitted from illustration in FIGS. 13 through 16 .

The voltage measuring device 200 A shown in FIG. 13 includes a battery assembly 12 having a module array 14 , which is made up of a plurality of (six) series-connected battery modules 16 ( 16 a through 16 f ), as many resistors 30 ( 30 a through 30 f ) as the number of modules 16 , and as many capacitors 232 a through 232 f as the number of modules 16 . The capacitors 232 a through 232 f are not connected in series, but have respective ends (positive pole sides) thereof, which are connected by non-reference lines 24 n to the positive pole sides of the respective modules 16 , and respective other ends (negative pole sides) thereof, which are connected to a reference line 24 ref that is free of a resistor 30 . The capacitors 232 a through 232 f shown in FIG. 13 correspond to the non-dividing capacitors (first capacitors). Therefore, RC filters made up of the resistors 30 and the capacitors 232 a through 232 f operate independently of each other.

The resistors 30 have respective resistance values R 20x denoted by R 201 through R 206 counted from the reference line 24 ref (upwardly in FIG. 13 ). The capacitors 232 a through 232 f have respective electrostatic capacitances C 21x denoted by C 211 through C 216 .

In FIG. 13 , it is assumed that the RC products (R 20x ·C 21x ) (where x represents an integer in a range from 1 through 6) of the RC filters are equal to each other, and that the voltages across respective modules 16 (module voltages Vm) are uniform. In this case, the RC filters have respective uniform output voltages of V 1 , V 2 , V 3 , V 4 , V 5 , and V 6 .

As shown in FIG. 14 , the capacitor 232 c shown in FIG. 13 can be replaced with three series-connected capacitors 232 g having an electrostatic capacitance C 233 , which is three times the electrostatic capacitance C 213 (C 233 =C 213 ×3). Since the voltage across the capacitors 232 g is divided into three equal voltages, as shown in FIG. 14 , the voltage at point E is equal to the voltage at point D. Likewise, the capacitor 232 e shown in FIG. 13 can be replaced with first series-connected capacitors 232 h having an electrostatic capacitance C 255 that is five times the electrostatic capacitance C 215 (C 255 =C 215 ×5). Since the voltage across the capacitors 232 h is divided into five equal voltages, as shown in FIG. 14 , the voltage at point G is equal to the voltages at points D and E, and the voltage at point H is equal to the voltage at point F.

Therefore, even if one of the midpoints (point E) between the capacitors 232 g (intermediate points between adjacent ones of the capacitors 232 g ) is connected to a corresponding line 24 , and two of the midpoints (point G and point H) between the capacitors 232 h (intermediate points between adjacent ones of the capacitors 232 h ) are connected to a corresponding line 24 , as shown in FIG. 15 , the output voltages V 1 through V 6 of the RC filters remain the same as those shown in FIG. 13 .

Furthermore, as shown in FIG. 16 , a group of parallel-connected capacitors shown in FIG. 15 is replaced with a single capacitor. More specifically, the single capacitor 232 b , the two capacitors 232 g , and the two capacitors 232 h , which are connected between the positive pole side of the module 16 b (points D, E, G shown in FIG. 15 ) and the line 24 connected to ground, are replaced with a single capacitor 232 i . The single capacitor 232 g and the single capacitor 232 h , which are connected between the positive pole side of the module 16 c (points F, H) and the line 24 connected to the negative pole side of the module 16 c (points E, G), are replaced with a single capacitor 232 j . Furthermore, the two capacitors 232 h , which are connected between the negative pole side of the module 16 d (point H) and the line 24 connected to the positive pole side of the module 16 e (point I), are replaced with a single capacitor 232 k . Even if such replacements are made, the output voltages V 1 through V 6 of the RC filters remain the same as those shown in FIG. 13 .

Assuming that the capacitors 232 b , 232 c , 232 e , 232 g , 232 h , 232 i , 232 j , 232 k have respective electrostatic capacitances C 212 , C 213 , C 215 , C 233 , C 255 , C 202 , C 203 , C 205 , then the electrostatic capacitances C 202 , C 203 , C 205 are determined by the following equations (4-1), (4-2), and (4-3), due to the relationships shown in FIGS. 13 through 16 .

If the time constant of each RC filter is represented by a particular constant τ, then the relationships according to the following equations (4-4), (4-5), and (4-6) are satisfied.

Based on equation (4-6), the resistance value R 205 of the resistor 30 e can be established according to the following equation (4-7).

The following equations (4-8) and (4-9) can be derived from equation (4-5) and equation (4-7).

The following equations (4-10) and (4-11) can be derived from equations (4-4), (4-7), and (4-9).

According to the above-described process, it is possible to establish the electrostatic capacitances C 202 , C 203 , C 205 of the dividing capacitors 232 i , 232 j , 232 k , and the resistance values R 202 , R 203 , R 205 of the resistors 30 b , 30 c , 30 e.

B-3. Specific Inventive Examples

B-3-1. Second Inventive Example

FIG. 17 is a diagram showing a specific example (second inventive example) of numerical values for the resistors 30 ( 30 a through 30 j ) and the capacitors 32 ( 32 a through 32 j ) in the arrangement of the voltage measuring device 10 A shown in FIG. 12 . As shown in FIG. 17 , a voltage measuring device 10 b according to the second inventive example has capacitors 32 a through 32 c , 32 e , 32 f , 32 h , 32 j , which serve as non-dividing capacitors 32 nd (first capacitors 32 nd ), and capacitors 32 d , 32 g , 32 i , which serve as dividing capacitors 32 div (second capacitors 32 div), used in combination. Consequently, it is possible to increase the degree of freedom with which the RC filters are designed, while at the same time lowering withstand voltage limits for the capacitors 32 .

The voltage measuring device 10 b shown in FIG. 17 is designed according to the following sequence, for example. First, a required time constant τ is established. According to the second inventive example, the time constant τ=100 μsec.

Thereafter, electrostatic capacitances C 20x of the capacitors 32 are determined. According to the second inventive example, the product of the electrostatic capacitances C 201 through C 203 , C 205 , C 206 , C 208 , and C 210 of the non-dividing capacitors 32 a through 32 c , 32 e , 32 f , 32 h , and 32 j , and the resistance values R 201 through R 203 , R 205 , R 206 , R 208 , and R 210 of the resistors 30 a through 30 c , 30 e , 30 f , 30 h , and 30 j , which are paired with the non-dividing capacitors 32 a through 32 c , 32 e , 32 f , 32 h , and 32 j , is represented by τ. Therefore, the electrostatic capacitances C 201 through C 203 , C 205 , C 206 , C 208 , and C 210 of the non-dividing capacitors 32 a through 32 c , 32 e , 32 f , 32 h , and 32 j can be established comparatively freely.

According to the second inventive example, each of the electrostatic capacitances C 201 through C 203 , C 205 , C 206 , C 208 , and C 210 of the non-dividing capacitors 32 a through 32 c , 32 e , 32 f , 32 h , and 32 j is established as 1 μF. Accordingly, each of the resistance values R 201 through R 203 , R 205 , R 206 , R 208 , and R 210 of the resistors 30 a through 30 c , 30 e , 30 f , 30 h , and 30 j is established as 100Ω.

The electrostatic capacitances C 204 , C 207 , C 209 of the dividing capacitors 32 d , 32 g , 32 i , which satisfy the above inequalities (3-1) and (3-2), are established as 3.3 μF each.

The resistance values R 204 , R 207 , and R 209 of the resistors 30 d , 30 g , and 30 i , which are paired with the dividing capacitors 32 d , 32 g , 32 i , are established as 121Ω, 212Ω, and 136Ω (rounded off to whole numbers), respectively, based on equations (3-3), (3-4), and (3-5) and the electrostatic capacitances C 204 , C 207 , and C 209 . In the inequalities and equations (3-1) through (3-5), L k1 , L k2 , L k3 (i.e., the numbers of the non-reference lines 24 n from the reference line 24 ref to the non-reference lines 24 n that are connected to the respective terminals of the capacitors 32 d , 32 g , 32 i , which are located remotely (toward the positive pole side) from the reference line 24 ref) are represented by 4, 7, and 9, respectively.

With the arrangement shown in FIG. 17 , similar to the case shown in FIG. 7 , it is possible to realize a certain time constant τ and to make the frequency characteristics of the RC filters uniform.

B-3-2. Third Inventive Example

FIG. 18 is a diagram showing a specific example (third inventive example) of numerical values for the resistors 30 ( 30 a through 30 j ) and the capacitors 32 ( 32 a through 32 j ) in an arrangement (modification of FIG. 12 ) that includes plural combinations of three RC filters. As shown in FIG. 18 , a voltage measuring device 10 c according to the third inventive example has a capacitor 32 a , which serves as a non-dividing capacitor 32 nd (first capacitor 32 nd ), and capacitors 32 b through 32 j , which serve as dividing capacitors 32 div (second capacitors 32 div), used in combination.

The dividing capacitors 32 b , 32 e , 32 h make up a first dividing capacitor group 36 a (first series-connected capacitor group 36 a ), the dividing capacitors 32 d , 32 g , 32 i make up a second dividing capacitor group 36 b (second series-connected capacitor group 36 b ), and the dividing capacitors 32 c , 32 f , 32 j make up a third dividing capacitor group 36 c (third series-connected capacitor group 36 c ). Consequently, it is possible to increase the degree of freedom with which the RC filters are designed, while at the same time lowering withstand voltage limits for the dividing capacitors 32 b through 32 j.

The voltage measuring device 10 c shown in FIG. 18 is designed according to the following sequence, for example. First, a required time constant τ is established. According to the third inventive example, the time constant τ=100 μsec.

Thereafter, electrostatic capacitances C 20x of the capacitors 32 are determined. According to the third inventive example, the product of the electrostatic capacitance C 201 of the non-dividing capacitor 32 a and the resistance value R 201 of the resistor 30 a , which is paired with the non-dividing capacitor 32 a , is represented by τ. Therefore, the electrostatic capacitance C 201 of the non-dividing capacitor 32 a can be established comparatively freely. According to the third inventive example, the electrostatic capacitance C 201 of the non-dividing capacitor 32 a is established as 1 μF. Accordingly, the resistance value R 201 of the resistor 30 a , which is paired with the non-dividing capacitor 32 a , is established as 100Ω.

The electrostatic capacitances C 202 through C 210 of the dividing capacitors 32 b through 32 j , which satisfy the above inequalities (3-1) and (3-2) for the first through third dividing capacitor groups 36 a through 36 c , are established as C 202 =4.7 μF, C 203 =C 204 =C 207 =C 209 =3.3 μF, C 205 =C 206 =2.2 μF, C 208 =C 210 =1 μF.

The resistance values R 202 through R 210 of the resistors 30 b through 30 j , which are paired with the dividing capacitors 32 b through 32 j , are established based on equations (3-3), (3-4), and (3-5) and the electrostatic capacitances C 202 through C 210 for the first through third dividing capacitor groups 36 a through 36 c . More specifically, R 202 =71Ω, R 203 =91Ω, R 204 =121Ω, R 205 =139Ω, R 206 =231Ω, R 207 =212Ω, R 208 =267Ω, R 209 =136Ω, R 210 =250Ω (rounded off to whole numbers).

With respect to the first dividing capacitor group 36 a , in the inequalities and equations (3-1) through (3-5), the numbers L k1 , L k2 , and L k3 (i.e., the numbers of the non-reference lines 24 n from the reference line 24 ref to the non-reference lines 24 n that are connected to the respective terminals of the capacitors 32 b , 32 e , 32 h , which are located remotely (toward the positive pole side) from the reference line 24 ref), are represented by 2, 5, and 8, respectively. With respect to the second dividing capacitor group 36 b , in the inequalities and equations (3-1) through (3-5), the numbers L k1 , L k2 , and L k3 (i.e., the numbers of the non-reference lines 24 n from the reference line 24 ref to the non-reference lines 24 n that are connected to the respective terminals of the capacitors 32 d , 32 g , 32 i , which are located remotely (toward the positive pole side) from the reference line 24 ref), are represented by 4, 7, and 9, respectively. With respect to the third dividing capacitor group 36 c , in the inequalities and equations (3-1) through (3-5), L k1 , L k2 , and L k3 (i.e., the numbers of the non-reference lines 24 n from the reference line 24 ref to the non-reference lines 24 n that are connected to the respective terminals of the capacitors 32 c , 32 f , 32 j , which are located remotely (toward the positive pole side) from the reference line 24 ref), are represented by 3, 6, and 10, respectively.

With the arrangement shown in FIG. 18 , similar to the case with FIG. 7 , it is possible to realize a certain time constant τ and to make the frequency characteristics of the RC filters uniform.

B-4. Advantages of the Second Embodiment

The second embodiment has an arrangement in which three RC filters are combined, whereas the third embodiment, to be described later, has an arrangement in which the number of combined RC filters is not limited (a more general arrangement). Therefore, the advantages of the second embodiment will be described in detail along with the advantages of the third embodiment.

C. Third Embodiment (Arrangement in which a Plurality of RC Filters are Combined)

C-1. Overall Arrangement

FIG. 19 is a circuit diagram showing a portion of a voltage measuring device 10 B according to a third embodiment of the present invention. The voltage measuring device 10 B according to the third embodiment has an arrangement in which the number of RC filters is not limited, which is provided by generalizing, respectively, the voltage measuring device 10 according to the first embodiment and the voltage measuring device 10 A according to the second embodiment.

More specifically, the voltage measuring device 10 B measures a voltage across a battery assembly 12 (i.e., module voltages Vm across respective modules 16 ) comprising a module array 14 made up of p series-connected battery modules 16 (where p represents an integer of 3 or greater). Although not shown in FIG. 19 , the voltage measuring device 10 B also includes the voltage measuring circuit 18 , the processor 20 , the switches 38 , and the controller 40 , similar to the case of the first embodiment ( FIG. 1 ).

The voltage measuring circuit 18 of the voltage measuring device 10 B is connected to positive and negative pole sides of the modules 16 by p+1 lines 24 , which are connected to junctions between the modules 16 and opposite ends of the module array 14 . Among the p+1 lines 24 , p lines 24 have p resistors 30 , respectively. The line 24 , which is free of a resistor 30 , is referred to as a “reference line 24 ref”, whereas the lines 24 having resistors 30 are referred to as “non-reference lines 24 n”.

The reference line 24 ref is positioned on the negative-most pole side (lowermost side in FIG. 19 ) of the module array 14 . However, as will be described later, the reference line 24 ref may be positioned at another location. The reference line 24 ref need not be a single reference line, but may be made up from a plurality of reference lines, as described later. The voltage measuring device 10 B includes p capacitors 32 , which are combined with the resistors 30 , thereby making up RC filters.

The capacitors 32 include non-dividing capacitors 32 nd (first capacitors 32 nd ), which are not connected in series to other capacitors 32 , and dividing capacitors 32 div (second capacitors 23 div), which are connected in series to other capacitors 32 . The dividing capacitors 32 div make up at least one dividing capacitor group 36 (series-connected capacitor group 36 ).

For illustrative purposes, the resistance value of each of the resistors is denoted by R 30x in FIG. 19 , where the subscript “x” represents an integer in a range from 1 to p, and indicates the location thereof counted from the reference line 24 ref. For example, the resistance value of the resistor 30 on the first non-reference line 24 n from the reference line 24 ref is denoted by R 301 . The total number of resistors 30 is represented by p.

Similarly, for illustrative purposes, the electrostatic capacitance of each of the capacitors 32 is denoted by C 30x in FIG. 19 , where the subscript “x” indicates the location counted from the reference line 24 ref, as described above. For example, the electrostatic capacitance of the first capacitor 32 from the reference line 24 ref is denoted by C 301 , and the electrostatic capacitance of the second capacitor 32 from the reference line 24 ref by C 302 . The total number of capacitors 32 is the same as the module number p. In FIG. 19 , “s”, “t”, and “u” represent integers that satisfy the inequality 3<s−1<s<t−1<t<u−1<u<p−1<p.

C-2. Basic Concept of Resistance Value R 30 , and Electrostatic Capacitance C 30n

A process of establishing the resistance value R 30n of a resistor 30 and the electrostatic capacitance C 30n of a capacitor 32 in accordance with the third embodiment will be described below. According to the third embodiment, in which plural RC filters are combined, the resistance value R 30n and the electrostatic capacitance C 30n are established in the following manner.

With respect to a non-dividing capacitor 32 nd , the resistance value R 30n and the electrostatic capacitance C 30n thereof are established such that the time constant of each RC filter will be of a characteristic value τ. Stated otherwise, the resistance value R 30n and the electrostatic capacitance C 30n can be set to any values, insofar as the product of the resistance value R 30n and the electrostatic capacitance C 30n is represented by τ.

With respect to a dividing capacitor 32 div, the following definitions are given in relation to the dividing capacitor group 36 .

n: the number of dividing capacitors 32 div

m: an integer in a range from 2 to n−1

q: an integer in a range from 1 to n

k q : the number of dividing capacitors 32 div from the reference line 24 ref to a dividing capacitor 32 div in question (including a dividing capacitor 32 div in question)

L kq : the number of non-reference lines 24 n from the reference line 24 ref to a non-reference line 24 n that is connected to the terminal of the k q th dividing capacitor 32 div remote from the reference line 24 ref (the positive pole side terminal of the dividing capacitor 32 div in FIG. 19 )

C kq : the electrostatic capacitance of the k q th dividing capacitor 32 div

R kq : the resistance value of the resistor 30 that is connected to the k q th dividing capacitor 32 div

In FIG. 19 , k 1 corresponds to the capacitor 32 having an electrostatic capacitance C 30s , k 2 corresponds to the capacitor 32 having an electrostatic capacitance C 30t , k 3 corresponds to the capacitor 32 having an electrostatic capacitance C 30u , and k 4 corresponds to the capacitor 32 having an electrostatic capacitance C 30p . The number L k1 corresponding to the capacitor 32 having the electrostatic capacitance C 30s is represented by “s”, the number L k2 corresponding to the capacitor 32 having the electrostatic capacitance C 30t is represented by “t”, the number L k3 corresponding to the capacitor 32 having the electrostatic capacitance C 30u is represented by “u”, and the number L k4 corresponding to the capacitor 32 having the electrostatic capacitance C 30p is represented by “p”.

According to the above definitions, the electrostatic capacitance C kq of each dividing capacitor 32 div is established to satisfy inequalities (5-1) and (5-2) below, and the resistance R kx of each resistor 30 is established to satisfy equations (5-3), (5-4), and (5-5) below.

C-3. Specific Examples

C-3-1. Fourth Inventive Example

FIG. 20 is a diagram showing a specific example (fourth inventive example) of numerical values for the resistors 30 ( 30 a through 30 j ) and the capacitors 32 ( 32 a through 32 j ) in the arrangement of the voltage measuring device 10 B shown in FIG. 19 . As shown in FIG. 20 , a voltage measuring device 10 d according to the fourth inventive example has capacitors 32 a , 32 d , 32 f , 32 g , 32 i , 32 j , which serve as non-dividing capacitors 32 nd (first capacitors 32 nd ), and capacitors 32 b , 32 c , 32 e , 32 h , which serve as dividing capacitors 32 div (second capacitors 32 div), used in combination. Consequently, it is possible to increase the degree of freedom with which the RC filters are designed, while at the same time lowering withstand voltage limits for the capacitors 32 .

The voltage measuring device 10 d shown in FIG. 20 is designed according to the following sequence, for example. First, a required time constant τ is established. According to the fourth inventive example, τ=100 μsec.

Thereafter, electrostatic capacitances C 30x of the capacitors 32 are determined. According to the fourth inventive example, the product of the electrostatic capacitances C 301 , C 304 , C 306 , C 307 , C 309 , C 310 of the non-dividing capacitors 32 a , 32 d , 32 f , 32 g , 32 i , 32 j and the resistance values R 301 , R 304 , R 306 , R 307 , R 309 , R 310 of the resistors 30 a , 30 d , 30 f , 30 g , 30 i , 30 j , which are paired with the non-dividing capacitors 32 a , 32 d , 32 f , 32 g , 32 i , 32 j , is represented by τ. Therefore, the electrostatic capacitances C 301 , C 304 , C 306 , C 307 , C 309 , C 310 of the non-dividing capacitors 32 a , 32 d , 32 f , 32 g , 32 i , 32 j can be established comparatively freely.

According to the fourth inventive example, each of the electrostatic capacitances C 301 , C 304 , C 306 , C 307 , C 309 , C 310 of the non-dividing capacitors 32 a , 32 d , 32 f , 32 g , 32 i , 32 j is established as 1 μF. Accordingly, each of the resistance values R 301 , R 304 , R 306 , R 307 , R 309 , R 310 of the resistors 30 a , 30 d , 30 f , 30 g , 30 i , 30 j , which are paired with the non-dividing capacitors 32 a , 32 d , 32 f , 32 g , 32 i , 32 j , is established as 100Ω.

The electrostatic capacitances C 302 , C 303 , C 305 , C 308 of the dividing capacitors 32 b , 32 c , 32 e , 32 h , which satisfy the above inequalities (5-1) and (5-2), are established as 4.7 μF, 6.8 μF, 2.2 μF, 1 μF, respectively.

The resistance values R 302 , R 303 , R 305 , R 308 of the resistors 30 b , 30 c , 30 e , 30 h , which are paired with the dividing capacitors 32 b , 32 c , 32 e , 32 h , are established based on equations (5-3), (5-4), and (5-5) and the electrostatic capacitances C 302 , C 303 , C 305 , C 308 . More specifically, R 302 =77Ω, R 303 =125Ω, R 305 =357Ω, R 308 =267Ω (rounded off to whole numbers).

In the inequalities and equations (5-1) through (5-5), the numbers L k1 , L k2 , L k3 , and L k4 (i.e., the numbers of the non-reference lines 24 n from the reference line 24 ref to the non-reference lines 24 n that are connected to the respective terminals of the capacitors 32 b , 32 c , 32 e , 32 h that are located remotely (toward the positive pole side) from the reference line 24 ref) are represented by 2, 3, 5, and 8, respectively.

With the arrangement shown in FIG. 20 , as shown in FIG. 7 , it is possible to realize a certain time constant τ and to make the frequency characteristics of the RC filters uniform.

C-3-2. Fifth Inventive Example

As described above, the reference line 24 ref need not necessarily be positioned on the negative-most pole side of the module array 14 . The reference line 24 ref may be positioned somewhere else.

FIG. 21 is a diagram showing a specific example (fifth inventive example) of numerical values for the resistors 30 ( 30 a through 30 j ) and the capacitors 32 ( 32 a through 32 j ) in an arrangement (modification of FIG. 19 ), which uses the positive-most pole line 24 of the module array 14 as the reference line 24 ref, and which has three dividing capacitor groups 36 (series-connected capacitor groups 36 ).

As shown in FIG. 21 , a voltage measuring device 10 e according to the fifth inventive example has a capacitor 32 j , which serves as a non-dividing capacitor 32 nd (first capacitor 32 nd ), and capacitors 32 a through 32 i , which serve as dividing capacitors 32 div (second capacitors 32 div), used in combination. The dividing capacitors 32 c , 32 f , 32 i make up a first dividing capacitor group 36 a (first series-connected capacitor group 36 a ). The dividing capacitors 32 b , 32 d , 32 g make up a second dividing capacitor group 36 b (second series-connected capacitor group 36 b ). The dividing capacitors 32 a , 32 e , 32 h make up a third dividing capacitor group 36 c (third series-connected capacitor group 36 c ). Consequently, it is possible to increase the degree of freedom with which the RC filters are designed, while at the same time lowering withstand voltage limits for the dividing capacitors 32 a through 32 i.

In FIG. 21 , for easier understanding of the fifth inventive example (by way of comparison with the first through fourth inventive examples), the term “x” in the resistance values R 30x of the resistors 30 represents an integer in a range from 0 to 9.

The voltage measuring device 10 e shown in FIG. 21 is designed according to the following sequence, for example. First, a required time constant τ is established. According to the fifth inventive example, τ=100 μsec.

Thereafter, electrostatic capacitances C 30 , of the capacitors 32 are determined. According to the fifth inventive example, the product of the electrostatic capacitance C 310 of the non-dividing capacitor 32 j and the resistance value R 309 of the resistor 30 j , which is paired with the non-dividing capacitor 32 j , is represented by τ. Therefore, the electrostatic capacitance C 310 of the non-dividing capacitor 32 j can be established comparatively freely. According to the fifth inventive example, the electrostatic capacitance C 310 of the non-dividing capacitor 32 j is established as 1 μF. Accordingly, the resistance value R 309 of the resistor 30 j , which is paired with the non-dividing capacitor 32 j , is established as 100Ω.

The electrostatic capacitances C 301 through C 309 of the dividing capacitors 32 a through 32 i , which satisfy the above inequalities (5-1) and (5-2) for the first through third dividing capacitors 36 a through 36 c , are established as C 301 =C 303 =1 μF, C 302 =C 304 =C 307 =C 308 =3.3 μF, C 305 =C 306 =2.2 μF, C 309 =4.7 μF.

In the fifth inventive example, as shown in FIG. 21 , the reference line 24 ref is positioned in an uppermost position. In the first dividing capacitor group 36 a , as shown in FIG. 21 , k 1 corresponds to the capacitor 32 i having an electrostatic capacitance C 309 , k 2 corresponds to the capacitor 32 f having an electrostatic capacitance C 306 , and k 3 corresponds to the capacitor 32 c having an electrostatic capacitance C 303 . In the second dividing capacitor group 36 b , k 1 corresponds to the capacitor 32 g having an electrostatic capacitance C 307 , k 2 corresponds to the capacitor 32 d having an electrostatic capacitance C 304 , and k 3 corresponds to the capacitor 32 b having an electrostatic capacitance C 302 . In the third dividing capacitor group 36 c , k 1 corresponds to the capacitor 32 h having an electrostatic capacitance C 308 , k 2 corresponds to the capacitor 32 e having an electrostatic capacitance C 305 , and k 3 corresponds to the capacitor 32 a having an electrostatic capacitance C 301 .

The resistance values R 300 through R 308 of the resistors 30 a through 30 i , which are paired with the dividing capacitors 32 a through 32 i , are established based on equations (5-3), (5-4), and (5-5) and the electrostatic capacitances C 301 through C 309 . More specifically, R 300 =250Ω, R 301 =136Ω, R 302 =267Ω, R 303 =212Ω, R 304 =231Ω, R 305 =139Ω, R 306 =121Ω, R 307 =91Ω, and R 308 =71Ω (rounded off to whole numbers).

In the first dividing capacitor group 36 a , the number L k1 corresponding to the capacitor 32 i having the electrostatic capacitance C 309 is represented by 2, the number L k2 corresponding to the capacitor 32 f having the electrostatic capacitance C 306 is represented by 5, and the number L k3 corresponding to the capacitor 32 c having the electrostatic capacitance C 303 is represented by 8. In the second dividing capacitor group 36 b , the number L k1 corresponding to the capacitor 32 g having the electrostatic capacitance C 307 is represented by 4, the number L k2 corresponding to the capacitor 32 d having the electrostatic capacitance C 304 is represented by 7, and the number L k3 corresponding to the capacitor 32 b having the electrostatic capacitance C 302 is represented by 9. In the third dividing capacitor group 36 c , the number L k1 corresponding to the capacitor 32 h having the electrostatic capacitance C 308 is represented by 3, the number L k2 corresponding to the capacitor 32 e having the electrostatic capacitance C 305 is represented by 6, and the number L k3 corresponding to the capacitor 32 a having the electrostatic capacitance C 301 is represented by 10.

With the arrangement shown in FIG. 21 , it is possible to realize a certain time constant τ and to make the frequency characteristics of the RC filters uniform, as shown in FIG. 7 .

C-3-3. Sixth Inventive Example

FIG. 22 is a diagram showing a specific example (sixth inventive example) of numerical values for the resistors 30 ( 30 a through 30 j ) and the capacitors 32 ( 32 a through 32 j ) in an arrangement (modification of FIG. 19 ), which uses the central line 24 of the module array 14 as the reference line 24 ref, and which has four dividing capacitor groups 36 (series-connected capacitor groups 36 ).

As shown in FIG. 22 , a voltage measuring device 10 f according to the sixth inventive example has capacitors 32 e , 32 f , which serve as non-dividing capacitors 32 nd (first capacitors 32 nd ), and capacitors 32 a through 32 d and 32 g through 32 j , which serve as dividing capacitors 32 div (second capacitors 32 div), used in combination.

The dividing capacitors 32 b , 32 d make up a first dividing capacitor group 36 a (first series-connected capacitor group 36 a ). The dividing capacitors 32 a , 32 c make up a second dividing capacitor group 36 b (second series-connected capacitor group 36 b ). The dividing capacitors 32 g , 32 i make up a third dividing capacitor group 36 c (third series-connected capacitor group 36 c ). The dividing capacitors 32 h , 32 j make up a fourth dividing capacitor group 36 d (fourth series-connected capacitor group 36 d ). Consequently, it is possible to increase the degree of freedom with which the RC filters are designed, while at the same time lowering withstand voltage limits for the dividing capacitors 32 a through 32 d and 32 g through 32 j.

As shown in FIG. 22 , the reference line 24 ref is positioned at the center of the module array 14 . Therefore, the first dividing capacitor group 36 a , which is made up of the dividing capacitors 32 b , 32 d , and the third dividing capacitor group 36 c , which is made up of the dividing capacitors 32 g , 32 i , form separate dividing capacitor groups. Likewise, the second dividing capacitor group 36 b , which is made up of the dividing capacitors 32 a , 32 c , and the fourth dividing capacitor group 36 d , which is made up of the dividing capacitors 32 h , 32 j , form separate dividing capacitor groups. On the other hand, the capacitors 32 e , 32 f are not dividing capacitors 32 div, but are non-dividing capacitors 32 nd.

In FIG. 22 , for easier understanding of the sixth inventive example (by way of comparison with the first through fifth inventive examples), the term “x” in the resistance values R 30x of the resistors 30 represents an integer that ranges from 0 to 4 and from 6 to 10.

The voltage measuring device 10 f shown in FIG. 22 is designed according to the following sequence, for example. First, a required time constant τ is established. According to the sixth inventive example, τ=100 μsec.

Thereafter, electrostatic capacitances C 30n of the capacitors 32 are determined. According to the sixth inventive example, the product of the electrostatic capacitances C 305 , C 306 of the non-dividing capacitors 32 e , 32 f and the resistance values R 304 , R 306 of the resistors 30 e , 30 f , which are paired with the non-dividing capacitors 32 e , 32 f , is represented by τ. Therefore, the electrostatic capacitances C 305 , C 306 of the non-dividing capacitors 32 e , 32 f can be established comparatively freely. According to the sixth inventive example, each of the electrostatic capacitances C 305 , C 306 of the non-dividing capacitors 32 e , 32 f is established as 1 μF. Accordingly, each of the resistance values R 304 , R 306 of the resistors 30 e , 30 f , which are paired with the non-dividing capacitors 32 e , 32 f , is established as 100Ω.

The electrostatic capacitances C 301 through C 304 and C 307 through C 310 of the dividing capacitors 32 a through 32 d and 32 g through 32 j , which satisfy the above inequalities (5-1) and (5-2), are established as C 301 =C 303 =C 304 =C 307 =C 308 =C 310 =2 μF, C 302 =C 309 =1.5 μF.

In the sixth inventive example, the reference line 24 ref is positioned centrally in the module array 14 . As shown in FIG. 22 , in the first dividing capacitor group 36 a , k 1 corresponds to the capacitor 32 d having an electrostatic capacitance C 304 , and k 2 corresponds to the capacitor 32 b having an electrostatic capacitance C 302 . In the second dividing capacitor group 36 b , k 1 corresponds to the capacitor 32 c having an electrostatic capacitance C 303 , and k 2 corresponds to the capacitor 32 a having an electrostatic capacitance C 301 . In the third dividing capacitor group 36 c , k 1 corresponds to the capacitor 32 g having an electrostatic capacitance C 307 , and k 2 corresponds to the capacitor 32 i having an electrostatic capacitance C 309 . In the fourth dividing capacitor group 36 d , k 1 corresponds to the capacitor 32 h having an electrostatic capacitance C 308 , and k 2 corresponds to the capacitor 32 j having an electrostatic capacitance C.

The resistance values R 300 through R 303 and R 307 through R 310 of the resistors 30 a through 30 d and 30 g through 30 j , which are paired with the dividing capacitors 32 a through 32 d and 32 g through 32 j , are established based on equations (5-3), (5-4), and (5-5) and the electrostatic capacitances C 301 through C 304 and C 307 through C 310 . More specifically, R 300 =R 310 =114Ω, R 301 =R 309 =133Ω, R 302 =R 308 =136Ω, and R 303 =R 307 =143Ω (rounded off to whole numbers).

In the dividing capacitor group 36 a , the number L k1 corresponding to the capacitor 32 d having the electrostatic capacitance C 304 is represented by 2, and the number L k2 corresponding to the capacitor 32 b having the electrostatic capacitance C 302 is represented by 4. In the second dividing capacitor group 36 b , the number L k1 corresponding to the capacitor 32 c having the electrostatic capacitance C 303 is represented by 3, and the number L k2 corresponding to the capacitor 32 a having the electrostatic capacitance C 301 is represented by 5. In the third dividing capacitor group 36 c , the number L k1 corresponding to the capacitor 32 g having the electrostatic capacitance C 307 is represented by 2, and the number L k2 corresponding to the capacitor 32 i having the electrostatic capacitance C 309 is represented by 4. In the fourth dividing capacitor group 36 d , the number L k1 corresponding to the capacitor 32 h having the electrostatic capacitance C 308 is represented by 3, and the number L k2 corresponding to the capacitor 32 j having the electrostatic capacitance C 310 is represented by 5.

With the arrangement shown in FIG. 22 , it is possible to realize a certain time constant τ and to make the frequency characteristics of the RC filters uniform, as shown in FIG. 7 .

C-3-4. Seventh Inventive Example

As described above, the reference line 24 ref need not necessarily be a single reference line, but may be a plurality of reference lines. In other words, if both non-dividing capacitors 32 nd and dividing capacitors 32 div can be realized, then a plurality of reference lines 24 ref may be provided. All or some of the non-dividing capacitors 32 nd can share the same reference line 24 ref, or the non-dividing capacitors 32 nd can be associated with different respective reference lines 24 ref. In order to realize the dividing capacitors 32 div, at least two capacitors 32 may be associated with a single reference line 24 ref. Therefore, the total number of reference lines 24 ref can range from 1 to a number produced by subtracting 1 from the total number p of the capacitors 32 .

FIG. 23 is a diagram showing a specific example (seventh inventive example) of numerical values for the resistors 30 ( 30 a through 30 j ) and the capacitors 32 ( 32 a through 32 j ) in an arrangement (modification of FIG. 19 ) that uses positive-most and negative-most pole lines of the module array 14 as reference lines 24 ref, and which has four dividing capacitor groups 36 (series-connected capacitor groups 36 ).

As shown in FIG. 23 , a voltage measuring device 10 g according to the seventh inventive example has capacitors 32 a , 32 j , which serve as non-dividing capacitors 32 nd (first capacitors 32 nd ), and capacitors 32 b through 32 i , which serve as dividing capacitors 32 div (second capacitors 32 div) used in combination. The dividing capacitors 32 b , 32 d make up a first dividing capacitor group 36 a (first series-connected capacitor group 36 a ). The dividing capacitors 32 c , 32 e make up a second dividing capacitor group 36 b (second series-connected capacitor group 36 b ). The dividing capacitors 32 g , 32 i make up a third dividing capacitor group 36 c (third series-connected capacitor group 36 c ). The dividing capacitors 32 f , 32 h make up a fourth dividing capacitor group 36 d (fourth series-connected capacitor group 36 d ). Consequently, it is possible to increase the degree of freedom with which the RC filters are designed, while at the same time lowering withstand voltage limits for the dividing capacitors 32 b through 32 i.

Since the voltage measuring device 10 g shown in FIG. 23 has two reference lines 24 ref, the total number of lines 24 is represented by the number of modules +2. More specifically, two lines 24 are connected between the modules 16 e and 16 f.

The voltage measuring device 10 g shown in FIG. 23 is designed according to the following sequence, for example. First, a required time constant τ is established. According to the seventh inventive example, τ=100 μsec.

Thereafter, electrostatic capacitances C 30n of the capacitors 32 are determined. According to the seventh inventive example, the product of the electrostatic capacitances C 301 , C 310 of the non-dividing capacitors 32 a , 32 j and the resistance values R 301 , R 310 of the resistors 30 a , 30 j , which are paired with the non-dividing capacitors 32 a , 32 j , is represented by τ. Therefore, the electrostatic capacitances C 301 , C 310 of the non-dividing capacitors 32 a , 32 j can be established comparatively freely. According to the seventh inventive example, each of the electrostatic capacitances C 301 , C 310 of the non-dividing capacitors 32 a , 32 j is established as 1 μF. Accordingly, each of the resistance values R 301 , R 310 of the resistors 30 a , 30 j , which are paired with the non-dividing capacitors 32 a , 32 j , is established as 100Ω.

The electrostatic capacitances C 302 through C 309 of the dividing capacitors 32 b through 32 i , which satisfy the above inequalities (5-1) and (5-2), are established as C 302 =C 303 =C 305 =C 306 =C 308 =C 309 =2.2 μF, C 304 =C 307 =1.5 μF.

In the seventh inventive example, the reference lines 24 ref are positioned at uppermost and lowermost positions in FIG. 23 . In the first dividing capacitor group 36 a shown in FIG. 23 , k 1 corresponds to the capacitor 32 b having an electrostatic capacitance C 302 , and k 2 corresponds to the capacitor 32 d having an electrostatic capacitance C 304 . In the second dividing capacitor group 36 b , k 1 corresponds to the capacitor 32 c having an electrostatic capacitance C 303 , and k 2 corresponds to the capacitor 32 e having an electrostatic capacitance C 305 . In the third dividing capacitor group 36 c , k 1 corresponds to the capacitor 32 i having an electrostatic capacitance C 309 , and k 2 corresponds to the capacitor 32 g having an electrostatic capacitance C 307 . In the fourth dividing capacitor group 36 d , k 1 corresponds to the capacitor 32 h having an electrostatic capacitance C 308 , and k 2 corresponds to the capacitor 32 f having an electrostatic capacitance C 306 .

The resistance values R 302 through R 309 of the resistors 30 b through 30 i , which are paired with the dividing capacitors 32 b through 32 i , are established based on equations (5-3), (5-4), and (5-5) and the electrostatic capacitances C 302 through C 309 . More specifically, R 302 =R 309 =143Ω, R 303 =R 308 =136Ω, R 304 =R 307 =133Ω, R 205 =R 306 =114Ω (rounded off to whole numbers).

In the first dividing capacitor group 36 a , the number L k1 corresponding to the capacitor 32 b having the electrostatic capacitance C 302 is represented by 2, and the number L k2 corresponding to the capacitor 32 d having the electrostatic capacitance C 304 is represented by 4. In the second dividing capacitor group 36 b , the number L k1 corresponding to the capacitor 32 c having the electrostatic capacitance C 303 is represented by 3, and the number L k2 corresponding to the capacitor 32 e having the electrostatic capacitance C 305 is represented by 5. In the third dividing capacitor group 36 c , the number L k1 corresponding to the capacitor 32 i having the electrostatic capacitance C 309 is represented by 2, and the number L k2 corresponding to the capacitor 32 g having the electrostatic capacitance C 307 is represented by 4. In the fourth dividing capacitor group 36 d , the number L k1 corresponding to the capacitor 32 h having the electrostatic capacitance C 308 is represented by 3, and the number L k2 corresponding to the capacitor 32 f having the electrostatic capacitance C 306 is represented by 5.

With the arrangement shown in FIG. 23 , similar to the case shown in FIG. 7 , it is possible to realize a certain time constant τ and to make the frequency characteristics of the RC filters uniform.

C-4. Advantages of the Third Embodiment

According to the third embodiment, as described above, it is possible to increase the degree of design freedom for the RC filters (low-pass filters), while at the same time lowering withstand voltage limits for the capacitors 32 (dividing capacitors 32 div).

More specifically, according to the third embodiment, the voltage measuring device includes a dividing capacitor group 36 having a plurality of dividing capacitors 32 div, which are connected in series through measurement nodes 44 . Therefore, compared with an arrangement in which all of the capacitors 32 are non-dividing capacitors 32 nd , it is possible to reduce the withstand voltage limits for the dividing capacitors 32 div that make up the dividing capacitor group 36 .

According to the third embodiment, furthermore, the capacitors 32 included in the RC filters associated with the respective battery modules 16 can independently be placed as non-dividing capacitors 32 nd or as dividing capacitors 32 div included within the dividing capacitor group 36 . Consequently, it is possible to increase the degree of freedom with which the capacitors 32 can be placed, compared with an arrangement in which all of the capacitors 32 are placed in series, i.e., an arrangement having only one dividing capacitor group 36 free of non-dividing capacitors 32 nd.

According to the third embodiment, the electrostatic capacitances C 30x of the dividing capacitors 32 div satisfy the relationships represented by inequalities (5-1) and (5-2), whereas the resistance values R 30x of the resistors 30 satisfy the relationships represented by equations (5-3), (5-4), and (5-5). Consequently, it is possible to make the frequency characteristics of the RC filters uniform. More specifically, with respect to the non-dividing capacitors 32 nd and the resistors 30 , which are paired with the non-dividing capacitors 32 nd to make up the RC filters, the product of the electrostatic capacitances C 30x of the non-dividing capacitors 32 nd and the resistance values R 30x of the resistors 30 serves as a time constant τ. Further, since the electrostatic capacitances C 30x of the dividing capacitors 32 div satisfy inequalities (5-1) and (5-2), and the resistance values R 30x of the resistors 30 paired with the dividing capacitors 32 div to make up the RC filters satisfy equations (5-3) through (5-5), the time constant τ of each of the RC filters is constant. Consequently, the RC filters, including any of the non-dividing capacitors 32 nd and the dividing capacitors 32 div, exhibit uniform filter frequency characteristics (filter time constants).

The electrostatic capacitances C 30x of the dividing capacitors 32 div satisfy inequalities (5-1) and (5-2). Therefore, by taking into account the term “(L k2 −L k1 )/L k1 ” in inequality (5-1) and the term “(L k(m+1) −L km )/(L km −L k(m−1) )” in inequality (5-2), it is possible to impart a relative degree of freedom to the electrostatic capacitances C 30x of the dividing capacitors 32 div, and to use inexpensive general-purpose capacitors for the dividing capacitors 32 div. For example, it is possible to equalize the electrostatic capacitances C 30x of the dividing capacitors 32 div by setting the term “(L k2 −L k1 )/L k1 ” in inequality (5-1) and the term “(L k(m+1) −L km )/(L km −L k(m−1) )” in inequality (5-2) to numerical values greater than 0 and less than or equal to 1.

On the other hand, compared with the choices available for the electrostatic capacitances of general-purpose capacitors, the choices available for the resistance values of general-purpose resistors are greater. Trimmer resistors, the resistance values of which are adjustable as desired, are also generally available. In addition, it is easy to adjust the resistance values by combining series-connected resistors and parallel-connected resistors. Consequently, it is easier to satisfy equations (5-3) through (5-5) for the resistors 30 than to select the capacitors 32 , thereby making it possible to minimize the cost of the voltage measuring device 10 B.

D. Modifications

The present invention is not limited to the above-described embodiments and inventive examples, but may employ various arrangements based on the present description, the scope of the patent claims, and the details illustrated in the drawings. For example, the present invention may employ the following alternative arrangements.

In the above embodiments and inventive examples, each of the modules 16 is connected to a single voltage measuring circuit 18 . However, two or more voltage measuring circuits 18 may be employed, insofar as the number of voltage measuring circuits 18 used is less than or equal to the number of modules.

In the above embodiments, general-purpose capacitors may be used as the capacitors 32 . However, the capacitors 32 need not necessarily be general-purpose capacitors, but may be customized capacitors.

In the above embodiments and the inventive examples, each of the non-dividing capacitors 32 nd and each of the dividing capacitors 32 div are connected to the same poles of the modules 16 . However, the present invention is not limited to such connections. In FIG. 23 , the first dividing capacitor group 36 a , the second dividing capacitor group 36 b , and the non-dividing capacitor 32 j may be excluded, and further, the modules 16 b through 16 e may be excluded, such that each of the non-dividing capacitors 32 nd and each of the dividing capacitors 32 div are connected to different poles of the modules 16 .