Output current monitoring circuit

1. Technical Field

The present disclosure is directed to current monitoring and in particular output current of a switching regulator to provide more efficient power management.

2. Background

A power management IC (PMIC) is useful in providing precise output monitoring of a switching regulator, wherein a more efficient power management is required, and the average output current is sensed, digitized and used for controlling processors, for example a storage gauge used in battery chargers. In present applications this is accomplished by monitoring a voltage across a precision resistor external to a PMIC. The drawback to the measuring voltage across a precision external resistor entails both cost and power loss. The additional cost comes from the precision resistor and the extra pins necessary to connect to the precision resistor, wherein the precision resistor causes an additional power loss.

U.S. Pat. No. 7,301,288 B2 (Green) is directed to a high speed buck control IC for constant LED current regulation. In U.S. Pat. No. 7,986,188 B2 (Fujiwara) an output current monitor circuit is directed to detection of current flowing through an output transistor. U.S. Pat. No. 8,026,636 B2 (Oh) is directed to an apparatus and method that allows main power supplied from either of two power output including power management integrated circuit (PMIC). U.S. Pat. No. 8,612,779 B2 (More et al.) is directed to a power management integrated circuit (PMIC) and related methods. In U.S. Pat. No. 8,627,119 B2 (Barnes et al.) a power management integrated circuit (PMIC) is directed to methods that have been achieved in support multiple applications. US 2003/0128485 A1 (Matsumoto) is directed to a switching power supply that includes an over current protection circuit. US 2013/0314062 A1 (Notman et al.) is directed to methods and apparatus for control of DC-DC converters. US 2014/0015507 A1 (Park et al.) is directed to an apparatus for supplying power in a mobile terminal.

In the prior art shown in FIG. 1A a precision resistor Rs is connected in a current path in which a current is to be measured as a voltage drop across the precision resistor. The voltage across the resistor is amplified and then connected to a continuous time sigma-delta analog to digital converter (CT-DS ADC), which produces a digital voltage output that is proportional to the current flowing through the precision resistor Rs.

In the prior art shown in FIG. 1B is a block diagram of the voltage mode CT-DS ADC where an integrator connects the amplified voltage across the sense resistor RS to a clocked comparator circuit, and is further connected to clocked logic to produce the continuous time sigma delta voltage signal. Whereas the digital output signal is sufficient to convert the analog current through Rs to a digital signal that can be used in the power management of switching power regulators, the external precision resistor causes extra power loss, extra signal pins and a precision resistor to be used adding to the power, cost and reliability to provide the current monitor.

It is an objective of the present disclosure to integrate the detection of current by using a replica transistor device to detect the amount of current flowing in an output stage of a buck switching regulator.

It is also an objective of the present disclosure to couple current from the replica transistor device to a current mode CT-DS ADC through an operational transconductor (OTA).

It is further an objective of the present disclosure to provide a separate current output of the OTA for feedback to the replica device and to the current mode CT_SD ADC.

In the preferred embodiment, output current of a buck switching regulator is monitored by coupling an NMOS replica transistor in parallel with the NMOS output transistor device (the replicated transistor) of the switching regulator. A feedback loop of an OTA device is connected to the source terminal of the NMOS replica device, which forces the voltage of the source terminal of the replica device to be at a virtual ground voltage, and therefore forces the same voltage drop across the NMOS replica device as the NMOS device of the buck switching regulator. Since the PMOS output transistor of the buck switching regulator is off when the NMOS replicated output transistor is powered on, the current of the NMOS replicated device flows through the LX node of the buck switching regulator. Since the replica device is effectively coupled in parallel with the NMOS replicated device, all of the current of the NMOS replica device also flows through the LX node of the buck switching regulator. Therefore, the replica NMOS device is a scaled down replica of the NMOS replicated device so as to add only a small portion of the current to the total current flowing through the LX node and the inductor of the buck switching regulator. Assuming variations in device parameters and process defects between the replicated NMOS transistor device of the buck regulator and the NMOS replica device are within permissible limits, the current through the replica device will be proportionally the same as the buck switching regulator output within an acceptable limit.

The OTA has two separate output currents of identical value. One of which is used in a feedback loop connected to the source terminal of the NMOS replica device, and the second output current that connects current to a current mode analog to digital converter, preferably a continuous time-sigma delta analog to digital converter (CT-SD ADC) because of power consumption. The ADC produces an output, which is a digital value of the current flowing through the replica NMOS transistor device. At the input of the OTA and within the feedback loop is a sample and hold circuit comprising a resistor and a capacitor. The switch of the sample and hold circuit is closed when the NMOS transistor of the buck switching regulator is on, and is open when the NMOS transistor is off. The capacitor of the sample and hold circuit is charged during the time that the NMOS transistor is on.

The sample and hold circuitry at the input to the OTA amplifier can cause an error, which is a result of not applying the sample and hold circuit to the current signal of the switching regulator when the PMOS transistor is on and the NMOS transistor is off. This error can be avoided by shorting the input to the OTA amplifier to ground when the NMOS transistor device of the buck switching regulator is off. The error can also be avoided by using both NMOS and PMOS sensing, which adds additional complexity to the input circuitry of the OTA amplifier.

This invention will be described with reference to the accompanying drawings, wherein:

FIG. 1A shows a measurement of a current of prior art, which outputs the current as a digital voltage;

FIG. 1B shows a voltage mode CT-SD ADC of prior art used to convert an analog voltage into a digital output;

FIG. 2 shows a measurement of the output current of a buck regulator of the present disclosure using a replica of the NMOS output device of the buck regulator;

FIG. 3 shows current and voltage waveforms of the buck switching regulator of the present disclosure; and

FIGS. 4A and 4 b shows the addition of switch settings used to eliminate a sampling signal error when the NMOS device is off.

In FIG. 2 is a diagram of the preferred embodiment of the present disclosure. A partial view of buck switching regulator 20 is shown connected to a current sense amplifier and digital output 21 integrated together on the same integrated circuit device. Within the buck switching regulator is shown the inductor L 1 , PMOS driver transistor P 1 and the NMOS driver transistor N 1 . Both driver transistors P 1 and N 1 and the inductor are connected to the LX node. A replica transistor N 2 located in the sense and digitizer circuitry 21 is coupled in parallel to a replicated transistor N 1 of the buck switching regulator 20 , wherein the drain of the replica transistor N 2 is connected to the LX node and therefore to the drain of N 1 . The source of N 1 is connected to ground, and source of the replica transistor N 2 is forced to a virtual ground by the operational transconductor (OTA). Thus the replica transistor N 2 parallels the replicated transistor N 1 , wherein both transistors have the same drain to source voltage.

The replica transistor N 2 is coupled in parallel to the replicated transistor N 1 by connecting the drain terminals of the N 1 and N 2 transistors together and then controlling the source terminal of N 2 with the feedback loop of the operational transconductor (OTA) so that the current drawn form the source terminal of N 2 produces a voltage equal to zero volts (ground) on the source terminal. A sample and hold circuit comprising resistor R 3 and capacitor C 3 is connected to the input of the OTA to sample and hold the input signal during the time that the NMOS transistor N 1 of the switching regulator is powered on and hold the value of the signal during the time that the NMOS transistor N 1 is switched off. Since the charge on the sample and hold circuitry is collected only when the NMOS transistor N 1 is powered on, an error in the sampling voltage can occur because the sampling voltage obtained during the on state of the NMOS is not identically the same as when the PMOS is on. It should be noted that using a replica PMOS transistor as well as the NMOS replica transistor N 2 could provide a balanced mode that would prevent the error signal noted above.

The current of the replica transistor N 2 flows through the LX node and the inductor L 1 of the buck switching regulator since the only other possible path is turned off caused by the PMOS transistor P 1 being turned off. If the current through the replicated transistor N 1 is to be the dominating current, then the current produced by the replica NMOS transistor N 2 must be a relatively small portion of the output current of the buck switching regulator that is produced by the NMOS transistor N 1 . To accomplish this, the replica transistor N 2 is a scaled down version of the replicated transistor N 1 , done in a proportional manner to produce a current in the replica transistor N 2 that is proportionally smaller than the current in the replicated transistor N 1 .

The output of the OTA has two current sources 23 that each produce an identical value of current. One current source is used to drive the feedback loop back to the source terminal of the replica transistor N 2 . The second current source is used to provide an analog value of the replica transistor current to the ADC for conversion into a digital current value. The ADC shown in FIG. 2 is an integrating type ADC, which is explicitly shown as a continuous time-sigma delta ADC 24 . Another integrating type ADC that could be used is an integrating dual slope integral ADC.

FIG. 3 shows key current and voltage for the buck switching regulator. In the top diagram is shown the inductor current driven by the NMOS and PMOS transistors. In the next diagram is the NMOS and PMOS transistor current with the emphasis being placed on the NMOS current. It should be noted that the NMOS and PMOS transistor are never on at the same time and the average current of both driver transistors, NMOS N 1 and PMOS P 1 is close to being the same value. The diagram of FIG. 3 also shows the sampling switch S 1 to be on only when the NMOS transistor N 1 of the buck switching regulator Is turned on.

In FIGS. 4A and 4B are shown potential solutions to the hold error which is cause by not using both the NMOS and the PMOS switching signals to charge the hold capacitor. Besides using both the NMOS and the PMOS transistors to charge the hold capacitor, shorting the inputs of the OTA during the time that the NMOS transistor is off as shown in FIG. 4A or disabling the sampling switch during the time that the NMOS transistor is off as shown in FIG. 4 b.

While the invention has been particularly shown and described with reference to preferred embodiments thereof, it will be understood by those skilled in the art that various changes in form and details may be made without departing from the spirit and scope of the invention.