Radio receiver and method for controlling radio receiver

This application is based upon and claims the benefit of priority from the prior Japanese Patent Application No. 2011-055735, filed on Mar. 14, 2011, the entire contents of which are incorporated herein by reference.

Embodiments described herein relate generally to a radio receiver and a method for controlling the radio receiver.

Generally, a radio receiver includes various analog circuits. Recently, in the radio receiver, a technology for replacing some of analog circuits with digital circuits is employed for the purpose of higher performance and miniaturization.

Conventionally, a function of correcting a deviation (IQ imbalance) between an in-phase component and a quadrature component of a radio signal, which is one of functions of the radio receiver, is implemented by the digital circuit. When receiving the radio signal, the digital circuit refers to a well-known portion of the radio signal, estimates an imbalance amount based on the referred portion (reference signal), and corrects the IQ imbalance based on the estimated imbalance amount.

However, in the radio signal, there is not only the IQ imbalance of the radio receiver, but also there are incomplete factors such as an IQ imbalance of a radio transmitter that transmits the radio signal and a communication distortion. Furthermore, the reference signal exists only in a limited frequency of the radio signal. Accordingly, correction accuracy of the imbalance amount is low.

On the other hand, there is a technology for providing a reference signal generator with the radio receiver in order to improve the correction accuracy of the imbalance amount. However, a circuit size and production cost of the radio receiver are increased by the reference signal generator.

FIG. 1 is a configuration diagram illustrating a radio receiver 10 of the first embodiment.

FIG. 2 is a graph illustrating a simulation result regarding an estimated error of amplitude imbalance in IQ signal of the first embodiment.

FIG. 3 is a graph illustrating a simulation result for an estimated error of phase imbalance in IQ signal of the first embodiment.

FIG. 4 is a configuration diagram illustrating a radio receiver 10 of the second embodiment.

FIG. 5 is a flowchart illustrating control processing of the second embodiment.

FIG. 6 is a configuration diagram illustrating the radio receiver 10 according to the third embodiment.

FIG. 7 is a flowchart illustrating control processing of the third embodiment.

FIG. 8(A) and FIG. 8(B) are graphs illustrating a relationship between an average power Pave and an instantaneous power Pi of the third embodiment.

Embodiments will now be explained with reference to the accompanying drawings.

In general, according to one embodiment, a radio receiver includes an antenna, a low-noise amplifier, a quadrature demodulator, an analog-to-digital converter (ADC), a first power calculator, a second power calculator, a correlation value calculator, a correction parameter generator, a corrector, a demodulator, and a controller. The antenna receives a radio signal. The low-noise amplifier amplifies an output signal of the antenna with a low noise. The quadrature demodulator demodulates an output signal of the low-noise amplifier, and generates an analog I signal of an in-phase component and an analog Q signal of a quadrature component. The ADC converts the analog I signal into a digital I signal of the in-phase component and converts the analog Q signal into a digital Q signal of the quadrature component. The first power calculator calculates a first power of the digital I signal. The second power calculator calculates a second power of the digital Q signal. The correlation value calculator calculates a correlation value between the digital I signal and the digital Q signal. The correction parameter generator generates a correction parameter based on the first power expected value, the second power expected value, and the correlation value between the digital I signal and the digital Q signal. The corrector performs a linear transform operation using the correction parameter, corrects an IQ imbalance of the digital I signal and the digital Q signal, and generates a corrected I signal and a corrected Q signal. The demodulator demodulates the corrected I signal and the corrected Q signal, and generates a demodulated signal. The controller generates a gain control signal in order to control a gain of the low-noise amplifier in such a manner that a thermal noise mixed by the low-noise amplifier is larger than a quadrature demodulation noise mixed by the quadrature demodulator and an analog-digital conversion noise mixed by the analog-digital converter. The low-noise amplifier is operated on the basis of the gain control signal.

First Embodiment

A first embodiment of the invention will be described. The first embodiment is an example in which a correction parameter is calculated in order to correct the IQ imbalance based on a first power of a digital I signal, a second power of a digital Q signal, and a correlation value between the digital I signal and the digital Q signal.

A configuration of a radio receiver according to the first embodiment will be described below. FIG. 1 is a configuration diagram illustrating a radio receiver 10 of the first embodiment.

The radio receiver 10 of FIG. 1 includes an antenna 11 , a Low Noise Amplifier (LNA) 12 , a quadrature demodulator 13 , a first Analog to Digital Converters (ADC) 141 , a second ADC 142 , a correction controller 15 , a corrector 16 , a demodulator 17 , and a controller 18 . The correction controller 15 includes a first power calculator 151 , a second power calculator 152 , a correlation value calculator 153 , and a correction parameter generator 154 .

The controller 18 generates a first gain control signal GC 1 for controlling a gain of the LNA 12 such that a thermal noise mixed by the LNA 12 is significantly larger than a quadrature demodulation noise mixed by the quadrature demodulator 13 and an Analog to Digital (AD) conversion noise mixed by the first ADC 141 and the second ADC 142 .

The antenna 11 receives a radio signal transmitted from a base station (not illustrated) or a radio transmitter (not illustrated).

The LNA 12 amplifies an output signal of the antenna 11 with a low noise based on the first gain control signal GC 1 . The thermal noise is mixed in the output signal of the LNA 12 . Because the thermal noise is significantly larger than an antenna noise, a noise component of the output signal of the LNA 12 is substantially equal to the thermal noise.

The quadrature demodulator 13 demodulates the output signal of the LNA 12 to generate an analog in-phase-channel signal (analog Isignal) Ai of an in-phase component and an analog quadrature-phase-channel signal (analog Q signal) Aq of a quadrature component. The quadrature demodulation noise is mixed in the analog I signal Ai and the analog Q signal Aq. Because the controller 18 generates the first gain control signal GC 1 , the quadrature demodulation noise is significantly smaller than the thermal noise. Accordingly, the noise component mixed in the analog I signal Ai and the analog Q signal Aq is substantially equal to the thermal noise.

The first ADC 141 converts the analog I signal Ai into a digital I signal Di. The second ADC 142 converts the analog Q signal Aq into a digital Q signal Dq. The digital I signal Di and the digital Q signal Dq are influenced by the IQ imbalance caused by the quadrature demodulator 13 , the first ADC 141 and the second ADC 142 . Accordingly, a phase of the digital I signal Di is deviated from an ideal in-phase component by an imbalance amount, and a phase of the digital Q signal Dq is deviated from an ideal quadrature component by the imbalance amount. The AD conversion noise is mixed in the digital I signal Di and the digital Q signal Di. Since the controller 18 generates the first gain control signal GC 1 , the AD conversion noise is significantly smaller than the thermal noise. Accordingly, the noise component mixed in the digital I signal Di and the digital Q signal Dq is substantially equal to the thermal noise.

The correction controller 15 uses an Additive White Gaussian Noise (AWGN) model to model the thermal noise mixed in the digital I signal Di and the digital Q signal Dq and the correction controller 15 generates a correction parameter Cp to correct the IQ imbalance.

The first power calculator 151 and the second power calculator 152 calculate the first power of the digital I signal Di and the second power of the digital Q signal Dq, respectively. The correlation value calculator 153 calculates the correlation value between the digital I signal and the digital Q signal. The correction parameter generator 154 generates the correction parameter Cp based on the first power, the second power, and the correlation value between the digital I signal and the digital Q signal.

The corrector 16 uses the correction parameter Cp to perform an IQ imbalance correction operation, corrects the IQ imbalance of the digital I signal Di and the digital Q signal Dq, and generates a corrected I signal Di′ and a corrected Q signal Dq′. For example, the IQ imbalance correction operation is a linear transform operation.

The demodulator 17 generates a first demodulation correlation value Mi of the corrected I signal Di′ and a second demodulation correlation value Mq of the corrected Q signal Dq′ based on a mutual correlation function of a well-known I component and a well-known Q component in the radio signal to be demodulated, and the demodulator 17 generates a demodulated signal based on the generated first demodulation correlation value Mi and the generated second demodulation correlation value Mq. For example, the demodulator 17 includes a matched filter that generates the demodulated signal based on the mutual correlation function and a memory (for example, ROM (Read Only Memory)) in which the well-known I component and the well-known Q component are stored.

An operating principle of the correction controller 15 will be described below.

In an ideal state in which the IQ imbalance does not exist, the thermal noise based on a Gaussian distribution is mixed in the digital I signal QI and the digital Q signal Dq. Assuming that n I is the digital I signal Di in the ideal state and n Q is the digital Q signal Dq in the ideal state, equations 1 and 2 hold. That is, as expressed in equation 1, both a first power expected value E[n I 2 ] and a second power expected value E[n Q 2 ] are expressed in the ideal state using a thermal noise parameter σ depending on magnitude of the thermal noise, and the first power expected value E[n I 2 ] is equal to the second power expected value E[n Q 2 ]. As expressed in equation 2, a correlation value E[n I n Q ] between the digital I signal Di and the digital Q signal Dq is 0 in the ideal state. That is, in the ideal state, there is no correlation between the digital I signal Di and the digital Q signal Dq.

On the other hand, in a normal state in which the IQ imbalance exists, as to the thermal noise mixed in the digital I signal Di and the digital Q signal Dq, the power expected values do not become equal to each other, but the power expected values are variables correlated with each other. Assuming that n I ′ is the digital I signal Di in the normal state and n Q ′ is the digital Q signal Dq in the normal state, equations 4 to 6 hold when influences of an IQ amplitude imbalance α and an IQ phase imbalance φ are expressed by an equation 3. As expressed in the equations 4 and 5, a first power expected value E[n I 2′] in the normal state differs from a second power expected value E[ Q 2′] in the normal state. As expressed in the equation 6, in the normal state, there is a correlation between the digital I signal Di and the digital Q signal Dq.

Therefore, the IQ amplitude imbalance α is expressed by an equation 7, and the IQ phase imbalance φ is expressed by an equation 8.

The first power calculator 151 estimates the first power expected value E[n I 2 ′] in the normal state based on an equation 9. The second power calculator 152 estimates the second power expected value E[n Q 2 ′] in the normal state based on an equation 10. The correlation value calculator 153 estimates a correlation expected value E[n I 2 ′n Q 2 ′] in the normal state based on the equation 11. In the equations 9 to 11, N is the number of samples (that is, the number of measured values of the digital I signal Di and the digital Q signal Dq), n I (t) is the digital I signal Di at a time t, and n Q (t) is the digital Q signal Dq at the time t.

In the actual estimation, since the infinite number of samples N is hardly obtained unlike the equations 9 to 11, the number of samples N is cut off at a certain finite value. At this point, using the equations 9 to 11, an estimate value <I 2 > of the first power expected value E[n I 2 ′], an estimate value <Q 2 > of the second power expected value E[n Q 2 ′], and an estimate value <IQ> of the correlation expected value E[n I 2 ′n Q 2 ′] are expressed by equations 12 to 14, respectively. The equations 12 to 14 mean that each of the first power calculator 151 , the second power calculator 152 , and the correlation value calculator 153 can be implemented by one multiplier, one adder, one register, and one divider. In the case of the fixed number of samples N, the divider can be eliminated.

The correction parameter generator 154 calculates the IQ amplitude imbalance α based on an equation 15 and calculates the IQ phase imbalance φ based on an equation 16. The IQ amplitude imbalance α indicates a difference in amplitude between the digital I signal Di and the digital Q signal Dq. The IQ phase imbalance φ indicates a difference in phase between the digital I signal Di and the digital Q signal Dq. The correction parameter generator 154 calculates a linear transform correction matrix to be set to the corrector 16 . Then the correction parameter generator 154 outputs the correction parameters Cp to the corrector 16 . The output correction parameters include the IQ amplitude imbalance α, the IQ phase imbalance φ, and the linear transform correction matrix.

Preferably the number of samples N is a sufficiently large value such that a difference (estimated error of imbalance in IQ signal) between the power expected value (the first power expected value and the second power expected value) and the estimate value (estimate values of the first power expected value and the second power expected value) is included in an allowable range. FIG. 2 is a graph illustrating a simulation result regarding an estimated error of amplitude imbalance in IQ signal of the first embodiment. FIG. 3 is a graph illustrating a simulation result for an estimated error of phase imbalance in IQ signal of the first embodiment. FIGS. 2 and 3 illustrate the simulation results when the thermal noise is modeled using the AWGN model under the conditions of a sampling frequency of 40 MHz and the number of samples of 300. From FIGS. 2 and 3 , for example, in a general-purpose wireless Local Area Network (LAN), it can be seen that the estimated error is sufficiently decreased for a measurement time of about 10 to about 100 ms.

According to the first embodiment, the correction controller 15 generates the correction parameter Cp by using the digital I signal Di and the digital Q signal Dq, so that the correction accuracy of the imbalance amount can be improved without increasing the circuit size and the production cost of the radio receiver 10 .

Particularly, it is not necessary to test the IQ imbalance in producing the radio receiver 10 , so that the production cost can be reduced. It is not necessary that a circuit for testing the IQ imbalance be provided in the radio receiver 10 , so that the circuit size of the radio receiver 10 can be reduced. The IQ imbalance is corrected by using the digital I signal Di and the digital Q signal Dq, so that the correction accuracy can be improved.

Second Embodiment

A second embodiment of the invention will be described. The second embodiment is an example in which a determination whether the correction parameter Cp can be generated is made by using the digital I signal Di and the digital Q signal Dq. The same description as in the first embodiment will not be repeated here.

A configuration of a radio receiver of the second embodiment will be described below. FIG. 4 is a configuration diagram illustrating a radio receiver 10 of the second embodiment.

The radio receiver 10 of FIG. 4 includes the antenna 11 , the LNA 12 , the quadrature demodulator 13 , the first ADC 141 , and the second ADC 142 , the correction controller 15 , the corrector 16 , the demodulator 17 , and the controller 18 . The antenna 11 , the LNA 12 , the first ADC 141 and the second ADC 142 , the corrector 16 , and the demodulator 17 are identical to those of the first embodiment.

The controller 18 generates the first gain control signal GC 1 for controlling the gain of the LNA 12 and a second gain control signal GC 2 for controlling a gain of the quadrature demodulator 13 such that the thermal noise mixed by the LNA 12 is significantly larger than the quadrature demodulation noise mixed by the quadrature demodulator 13 and the AD conversion noise mixed by the first ADC 141 and the second ADC 142 .

The controller 18 generates a correction control signal CNT in order to control the operation of the correction controller 15 . More specifically, the controller 18 determines whether the correction parameter Cp can be generated on the basis of the digital I signal Di and the digital Q signal Dq. When the correction parameter Cp can be generated, the controller 18 generates an enable signal CNT(E) in order to operate the correction controller 15 . When the correction parameter Cp cannot be generated, the controller 18 generates a disable signal CNT(D) in order to stop the correction controller 15 .

The quadrature demodulator 13 demodulates the output signal of the LNA 12 to generate the analog I signal Ai and the analog Q signal Aq based on the second gain control signal GC 2 . The quadrature demodulation noise is mixed in the analog I signal Ai and the analog Q signal Aq. Because the controller 18 generates the first gain control signal GC 1 and the second gain control signal GC 2 , the quadrature demodulation noise is significantly smaller than the thermal noise. Accordingly, the noise component which is mixed in the analog I signal Ai and the analog Q signal Aq is substantially equal to the thermal noise.

When the controller 18 generates the enable signal CNT(E), the correction controller 15 models the thermal noise, which is mixed in the digital I signal Di and the digital Q signal Dq, by using the AWGN model. Then, the controller 18 generates the correction parameter Cp in order to correct the IQ imbalance. On the other hand, when the controller 18 generates the disable signal CNT(D), the correction controller 15 stops generation of the correction parameter Cp.

An operation of the radio receiver of the second embodiment of the invention will be described. FIG. 5 is a flowchart illustrating control processing of the second embodiment.

<S 500 > The controller 18 generates the first gain control signal GC 1 and the second gain control signal GC 2 . The LNA 12 and the quadrature demodulator 13 are operated on the basis of the first gain control signal GC 1 and the second gain control signal GC 2 . Therefore, the thermal noise is significantly larger than the quadrature demodulation noise.

<S 502 > The controller 18 generates the enable signal CNT(E). When receiving the enable signal CNT(E), the correction controller 15 starts the generation of the correction parameter Cp.

<S 504 > The controller 18 monitors the digital I signal Di and the digital Q signal Dq, and the controller 18 calculates a measured power Pm based on the digital I signal Di and the digital Q signal Dq. More specifically, the controller 18 calculates the measured power Pm based on an equation 17. In the equation 17, m is the number of bits of the digital I signal Di and the digital Q signal Dq, Vrange is an input range [V] of the first ADC 141 and the second ADC 142 , Zin is an input impedance [Ω] of the first ADC 141 and the second ADC 142 , K is the number of smoothed samples. Moreover, Di(t) and Dq(t) are signal levels of the digital I signal Di and the digital Q signal Dq at the time t, respectively.

<S 506 > The controller 18 determines whether the correction parameter Cp can be generated (that is, whether the antenna 11 receives the radio signal) based on a difference between a measured power Pm and a power threshold Pth. When the measured power Pm is larger than the power threshold Pth (YES in S 506 ), the controller 18 performs S 518 . On the other hand, when the measured power Pm is equal to or smaller than the power threshold Pth (NO in S 506 ), the controller 18 performs. S 508 .

The fact that the measured power Pm is larger than the power threshold Pth means that the correction parameter Cp cannot be generated (that is, the correction parameter Cp for the proper correction cannot be generated) because the digital I signal Di and the digital Q signal Dq are influenced by the radio signal. For example, when the antenna 11 receives the radio signal during generation of the correction parameter Cp, the digital I signal Di and the digital Q signal Dq are influenced by the radio signal. Therefore, the measured power Pm is larger than the power threshold Pth.

On the other hand, the fact that the measured power Pm is equal to or smaller than the power threshold Pth means that the correction parameter Cp can be generated (that is, the correction parameter Cp for the proper correction can be generated) because the digital I signal Di and the digital Q signal Dq are not influenced by the radio signal.

The controller 18 calculates the power threshold Pth based on an equation 18. In the equation 18, Pn is a predetermined thermal noise power expected value, and Po is an offset value. The controller 18 also calculates the thermal noise power expected value Pn based on an equation 19. In the equation 19, k is a Boltzmann constant, T is an operating temperature of the LNA 12 , B is a noise band width of the LNA 12 , NF is a noise index of the radio receiver 10 , and G is a sum of gains of the LNA 12 and the quadrature demodulator 13 .

[Formula 18]

Pth [dBm]= Pn [dBm]+ Po   (equation 18)

[Formula 19]

Pn [dBm]=10 log kT [dBm/Hz]+10 log B [Hz]+ NF [dB]+ G [dB]  (equation 19)

<S 508 > The controller 18 determines whether the generation of the correction parameter Cp is completed. When the generation of the correction parameter Cp is completed (YES in S 508 ), the control processing is ended. On the other hand, when the generation of the correction parameter Cp is not completed (NO in S 508 ), the flow returns to S 504 .

<S 518 > The controller 18 generates the disable signal CNT(D). When receiving the disable signal CNT(D), the correction controller 15 stops the generation of the correction parameter Cp.

In the second embodiment, the controller 18 may perform S 500 after a predetermined time elapses since the disable signal CNT(D) is generated.

In the second embodiment, in S 504 , instead of calculating the measured power Pm based on the digital I signal Di and the digital Q signal Dq, the controller 18 may calculate the measured power Pm based on the corrected I signal Di′ and the corrected Q signal Dq′. This is because the IQ imbalance correction operation does not largely change the signal level (that is, the signal levels of the digital I signal Di and the digital Q signal Dq are substantially equal to the signal levels of the corrected I signal Di′ and the corrected Q signal Dq′).

According to the second embodiment, the controller 18 determines whether the correction parameter Cp for the proper correction can be generated on basis of the digital I signal Di and the digital Q signal Dq. Moreover, the controller 18 controls the correction controller 15 such that the generation of the correction parameter Cp is stopped when the correction parameter Cp cannot be generated. Therefore, the generation of the correction parameter Cp, which causes the improper correction, can be prevented, and the correction accuracy of the imbalance amount can be improved better than that of the first embodiment.

Third Embodiment

A third embodiment of the invention will be described. In the second embodiment, whether the correction parameter Cp can be generated is determined on the basis of the digital I signal Di and the digital Q signal Dq. On the other hand, the third embodiment is an example in which the determination whether the correction parameter Cp can be generated is made on the basis of the correlation value which is the output of the matched filter in the demodulator. The same description as in the first and second embodiments will not be repeated here.

A configuration of a radio receiver of the third embodiment will be described below. FIG. 6 is a configuration diagram illustrating the radio receiver 10 according to the third embodiment.

The radio receiver 10 of FIG. 6 includes the antenna 11 , the LNA 12 , the quadrature demodulator 13 , the first ADC 141 , the second ADC 142 , the correction controller 15 , the corrector 16 , the demodulator 17 , and the controller 18 . The antenna 11 , the LNA 12 , the quadrature demodulator 13 , the first ADC 141 and the second ADC 142 , the corrector 16 , and the demodulator are identical to those of the first embodiment. The correction controller 15 is identical to that of the second embodiment.

The controller 18 generates the first gain control signal GC 1 for controlling the gain of the LNA 12 such that the thermal noise mixed by the LNA 12 is significantly larger than the quadrature demodulation noise mixed by the quadrature demodulator 13 and the AD conversion noise mixed by the first ADC 141 and the second ADC 142 .

The controller 18 generates the correction control signal CNT in order to control the operation of the correction controller 15 . More specifically, the controller 18 determines whether the correction parameter Cp can be generated on the basis of the first demodulation correlation value Mi and the second the first demodulation correlation value Mq. When the correction parameter Cp can be generated, the controller 18 generates the enable signal CNT(E) in order to operate the correction controller 15 . When the correction parameter Cp cannot be generated, the controller 18 generates the disable signal CNT(D) in order to stop the correction controller 15 .

An operation of the radio receiver of the third embodiment will be described below. FIG. 7 is a flowchart illustrating control processing of the third embodiment. FIG. 8 is a graph illustrating a relationship between an average power Pave and an instantaneous power Pi of the third embodiment.

<S 700 > The controller 18 generates the first gain control signal GC 1 . The LNA 12 is operated on the basis of the first gain control signal GC 1 . Therefore, the thermal noise is significantly larger than the quadrature demodulation noise.

<S 702 > The processing in S 702 is identical to that (S 502 of FIG. 5 ) of the second embodiment.

<S 704 > The controller 18 calculates the instantaneous power Pi of the matched filter at the time t based on an equation 20. In the equation 20, Mi(t) is the first demodulation correlation value at the time t, and Mq(t) is the second demodulation correlation value at the time t.

[Formula 20]

Pi= 10 log( M I 2 ( t )+ M Q 2 ( t ))  (equation 20)

<S 705 > The controller 18 calculates the average power Pave of the matched filter up to the time t based on an equation 21. In the equation 21, K is the number of samples used to calculate the average power Pave.

<S 706 > The controller 18 determines whether the correction parameter Cp can be generated (that is, whether the antenna 11 receives the radio signal) on the basis of a difference between the instantaneous power Pi and the average power Pave. When the instantaneous power Pi is larger than a value in which a proper offset value Po is added to the average power Pave (YES in S 708 ), the controller 18 performs S 718 . On the other hand, when the instantaneous power Pi is equal to or smaller than the sum (Pave+Po) of the average power Pave and a predetermined offset value Po (for example, 10 [dB]) (NO in S 706 ), the controller 18 performs S 708 .

As illustrated in FIG. 8B , the fact that the instantaneous power Pi is larger than the sum (Pave+Po) of the average power Pave and the offset value Po means that the correction parameter Cp for the proper correction cannot be generated because the digital I signal Di and the digital Q signal Dq are influenced by the radio signal. For example, when the antenna 11 receives the radio signal during generation of the correction parameter Cp, the digital I signal Di and the digital Q signal Dq are influenced by the radio signal, and the instantaneous power Pi is larger than the sum (Pave+Po) of the average power Pave and the offset value Po.

On the other hand, as illustrated in FIG. 8A , the fact that the instantaneous power Pi is equal to or smaller than the sum (Pave+Po) of the average power Pave and the offset value Po means that the correction parameter Cp for the proper correction can be generated because the digital I signal Di and the digital Q signal Dq are not influenced by the radio signal.

<S 708 and S 718 > The pieces of processing in S 708 and S 718 are identical to those (S 508 and S 518 of FIG. 5 ) of the second embodiment.

In the third embodiment, the controller 18 may perform S 700 after a predetermined time elapses since the disable signal CNT(D) is generated.

According to the third embodiment, the controller 18 determines whether the correction parameter Cp for the proper correction can be generated by using the first demodulation correlation value Mi and the second demodulation correlation value Mq, which are the outputs of the matched filter in the demodulator 17 . Moreover, the controller 18 controls the correction controller 15 such that generation of the correction parameter Cp is stopped when the correction parameter Cp cannot be generated. Therefore, generation of the correction parameter Cp, which causes the improper correction, can be prevented, and the correction accuracy of the imbalance amount can be improved better than that of the first and second embodiments. Particularly, in the third embodiment, the correction accuracy of the imbalance amount can be improved better than that of the second embodiment when a signal waveform of the radio signal is previously learned.

At least a portion of the radio receiver 10 according to the above-described embodiments may be composed of hardware or software. When at least a portion of the radio receiver 10 is composed of software, a program for executing at least some functions of the radio receiver 10 may be stored in a recording medium, such as a flexible disk or a CD-ROM, and a computer may read and execute the program. The recording medium is not limited to a removable recording medium, such as a magnetic disk or an optical disk, but it may be a fixed recording medium, such as a hard disk or a memory.

In addition, the program for executing at least some functions of the radio receiver 10 according to the above-described embodiment may be distributed through a communication line (which includes wireless communication) such as the Internet. In addition, the program may be encoded, modulated, or compressed and then distributed by wired communication or wireless communication such as the Internet. Alternatively, the program may be stored in a recording medium, and the recording medium having the program stored therein may be distributed.

While certain embodiments have been described, these embodiments have been presented by way of example only, and are not intended to limit the scope of the inventions. Indeed, the novel methods and systems described herein may be embodied in a variety of other forms; furthermore, various omissions, substitutions and changes in the form of the methods and systems described herein may be made without departing from the spirit of the inventions. The accompanying claims and their equivalents are intended to cover such forms or modifications as would fall within the scope and spirit of the inventions.