Uplink feedback for supporting MIMO operation in the LTE downlink

This application makes reference to, incorporates the same herein, and claims all benefits accruing under 35 U.S.C. §119 from an application earlier filed in the U.S. Patent & Trademark Office on 7 Dec. 2007 and there duly assigned Ser. No. 60/996,858.

1. Field of the Invention

The present invention relates to a method of transmission of channel quality information (CQI) and apparatus for utilizing such method in a Multiple Input Multiple Output (MIMO) system, and more specifically, to a quantization method of transmission of channel quality information (CQI) based on values of codewords, and apparatus for utilizing such method in the Multiple Input Multiple Output (MIMO) system.

2. Description of the Related Art

In an Orthogonal Frequency Division Multiplexing (OFDM) system, data may be transmitted by a transmitter and received by a receiver. At the transmitter, the input data may be sequentially processed by a quadrature amplitude modulation (QAM) modulator, a serial-to-parallel convertor, an inverse fast Fourier transform (IFFT) unit, and a parallel-to-serial convertor and a cyclic prefix (CP) inserter. The resulting sequence of samples is referred to as OFDM symbol. At the receiver, the transmitted data from the transmitter is sequentially processed by a cyclic prefix remover, a parallel-to-serial convertor, a fast Fourier transform (FFT) transformer, a parallel-to-serial convertor and a QAM demodulator. And therefore, the transmitted data may be recovered at the receiver.

Multiple Input Multiple Output (MIMO) schemes use multiple transmitting antennas and multiple receiving antennas in order to improve the capacity and reliability of a wireless communication channel. A MIMO system promises linear capacity with K where K is the minimum of number of transmitting antennas (M) at transmitter and receiving antennas (N) at receiver. As one example, four different data streams Data Streams are transmitted separately from the four transmitting antennas. The transmitted signals are received at four receiving antennas. Spatial signal processing may be performed on the received signals by a spatial signal processor in order to recover the four received data streams.

In the contemporary specifications of the LTE (long term evolution), codewords may be employed and mapped to up to four data transmission layers in the MIMO transmission.

As an example, in a four by four MIMO system, two codewords may be employed. The feedback of channel quality information (CQI) in the case of two-codeword MIMO transmission has been discussed in several 3GPP (third Generation Partnership Project) RAN1 contributions. An employment of CQI base and CQI delta in the feedback of CQI is the preferred approach in the contemporary LTE, because it may reduce the feedback overhead in the uplink by assigning fewer feedback bits for CQI delta than for CQI base . Here, CQI base is one of the two CQIs respectively defined for one of the two codewords respectively defined for each data transmission layer, and CQI delta is a difference between the two CQIs.

Recent research, however, discovers that the performance loss of the above stated “CQI base +CQI delta ” scenario may lead to potential performance loss in certain scenarios where the dynamic range of the CQI delta may vary significantly in different configurations and channel situations. Therefore, the contemporary scenario of “CQI base +CQI delta ” has a limited compression potential.

It is therefore one object of the present invention to provide an improved method of transmission of channel quality information (CQI) and apparatus for utilizing such method in a Multiple Input Multiple Output (MIMO) system in order to solve the above stated problems.

It is another object of the present invention to provide a quantization method of transmission of channel quality information (CQI) corresponding to certain values measured on codewords, and apparatus for utilizing such method in a Multiple Input Multiple Output (MIMO) system.

In a two-codeword MIMO system, CQI base and CQI delta are obtained by quantizing the measured value made on the two codewords in the MIMO transmission. Possible measured values made on the codewords include effective SINR (signal to interference plus noise ratio), i.e., EESM (exponential effective signal SIR/SNR Mapping), modulation-constrained mutual information, and other related values. SINR 1 and SINR 2 , which are observed at the user equipment (UE), are respectively denoted as the values made on two distinct codewords.

Configurable step size u S for small/zero delay CDD precoding schemes and configurable step size u L for large delay CDD schemes for quantization of the CQI delta may be determined either according to the antenna configuration (such as antenna spacing) of a cell including E-NodeB (base station) and corresponding UEs, or according to the channel condition of a given UE. Here, configurable offset o S may be defined for small/zero delay CDD preceding schemes and o L may be defined for large delay CDD schemes. The value of step sizes u S and u L may have a predetermined relationship. For example, step size u S may be equal to step size, or step size u S may be two times greater than step size u L . Some or all of variables u S and u L may be configured in a cell-specific fashion, and are carried and transmitted by one of the E-NodeB (i.e., eNB) broadcast messages.

Some or all of variables u S and u L may be configured in a UE-specific fashion, and are carried and transmitted by one of the higher-layer messages transmitted from e-NodeB to a UE semi-statically using, for example, a radio resource control (RRC) message.

Some or all of variables o S and o L may be configured in a UE-specific fashion, and are carried and transmitted by one of the higher-layer messages transmitted from e-NodeB to a UE semi-statically using, for example, a radio resource control (RRC) message.

At the UE side, the UE may receive these cell-specific or UE-specific variables mentioned above, construct proper quantization tables for CQI delta , and then report CQI delta and CQI base to the E-NodeB. Here, the quantization table for CQI base is known.

The quantization procedural steps includes that firstly, the UE measures SINRs respectively on two codewords and thus obtains SINR 1 and calculates delta SINR (i.e., (SINR 2 -SINR 1 )); secondly, the UE performs the quantization of CQI base calculating the CQI base based on the measured SINR 1 and a known quantization table for CQI base , and the UE simultaneously receives the cell-specific or UE-specific parameters transmitted from the E-NodeB and configures a quantization table for CQI delta and performs the quantization of CQI delta by calculating the CQI delta based on the calculated delta SINR and configured quantization table for CQI delta ; and thirdly, the UE reports CQI delta and CQI base to the E-NodeB.

On the other hand, the E-NodeB receives CQI base and CQI delta from the UE feedback in the uplink channel, and the E-NodeB performs the reversed operation compared to the UE and looks up the quantization tables in order to figure out the quantized SINR 1 and the quantized Delta SINR (SINR 2 -SINR 1 ).

In order to fully define the mapping between CQI delta and the quantized delta SINR (SINR 2 -SINR 1 ) value, a predetermined quantization table between CQI delta and an intermediate variable denoted by c is firstly constructed. In the uniform mapping example, the step size of the variable c is constant while the value of CQI delta increases. In one example of the non-uniform mappings, the step size in the variable c may be less in the middle portion of the table (i.e., the portion where CQI delta has mediate values among all of the available values) and greater towards the two ending portions (i.e., the portions where CQI delta has either greater values or less values compared to the mediate values among all of the available values). In another example of the non-uniform mappings, the step size in the variable c increases while the value of CQI delta increases.

The value of Delta SINR (SINR 2 -SINR 1 ) may be given by the following expressions: for small-delay or zero-delay CDD preceding,

o S +c·u S (dB); and

for large-delay CDD precoding,

o L +c·u L (dB)

where o S and o L refer to configurable offsets respectively for small-delay or zero-delay CDD preceding and large-delay CDD preceding, u S and u L refer to configurable steps respectively for small-delay or zero-delay CDD precoding and large-delay CDD preceding, and c is intermediate variable as stated above.

A more complete appreciation of the invention, and many of the attendant advantages thereof, will be readily apparent as the same becomes better understood by reference to the following detailed description when considered in conjunction with the accompanying drawings in which like reference symbols indicate the same or similar components, wherein:

FIG. 1 shows a simplified example of data transmission/reception using Orthogonal Frequency Division Multiplexing (OFDM);

FIG. 2 shows a simplified example of a 4×4 Multiple Input Multiple Output (MIMO) system;

FIG. 3 shows an example of a procedure of obtaining a measurement of SINRs (signal to interference plus noise ratio) averaged over several subbands and obtaining the channel quality information (CQI) according to the obtained SINRs according to the principle of one embodiment of the present invention; and

FIG. 4 is flow charts illustrating processes of the quantization of CQI delta and CQI base according to the principle of one embodiment of the present invention.

Six references as listed below are referred to and incorporated by reference into this application for the present invention:

[1] R1-072038, “UL Control Signaling in Support of DL SIMO and 2×2 SU-MIMO Users”, Qualcomm Europe, 3GPP TSG RAN WG1#49, Kobe, Japan, May 7-11, 2007;

[2] R1-072213, “Design Aspects of MIMO-Related UE Feedback”, Texas Instruments, 3GPP TSG RAN WG1#49, Kobe, Japan, May 7-11, 2007;

[3] R1-073489, “Delta CQI in spatial domain for SU-MIMO”, LG Electronics, 3GPP TSG RAN WG1#50, Athens, Greece, Aug. 20-24, 2007;

[4] R1-074655, “Limitations of CQI Compression for Dual Codeword MIMO”, Alcatel-Lucent, RAN1#51, Jeju, Korea, November 2007;

[5] R1-072001, 3GPP, “Draft Report of 3GPP TSG RAN WG1#48b v0.3.0”, Kobe, Japan, 7-11 May, 2007; and

[6] 3GPP TS36.21 1. v8.0.0. “EUTRA: Physical Channels and Modulation”, September 2007.

OFDM is a technology of multiplexing data in a frequency domain. Modulation symbols are carried by sub-carriers in a frequency demain. A simplified example of data transmission/reception using Orthogonal Frequency Division Multiplexing (OFDM) is shown in FIG. 1 . At a transmitter, data 100 to be transmitted is modulated by a quadrature amplitude modulation (QAM) modulator 111 . The QAM modulated symbols are serial-to-parallel converted by a serial-to-parallel convertor 113 . The QAM modulated symbols are serial-to-parallel converted by a serial-to-parallel convertor 113 and input to an inverse fast Fourier transform (IFFT) unit 115 . At the output of IFFT unit 115 , a number of N time-domain samples are obtained and N refers to the sampling number of IFFT/FFT used by the OFDM system. Signal output from IFFT unit 115 is parallel-to-serial converted by a parallel-to-serial convertor 117 and a cyclic prefix (CP) is added to the signal sequence by a CP inserter 119 . The resulting sequence of samples is referred to as OFDM symbol. At a receiver, the cyclic prefix is firstly removed by cyclic prefix remover 121 from the received OFDM symbols, and the output signal from cyclic prefix remover 121 is serial-to-parallel converted by parallel-to-serial convertor 123 before feeding the converted parallel signal into fast Fourier transform (FFT) transformer 125 . Output of FFT 125 is parallel-to-serial converted by parallel-to-serial convertor 127 and the resulting output is input to the QAM demodulator 129 . Therefore, the transmitted data is recovered at the receiver. The data is therefore transmitted by the transmitter and received by the receiver by using the Orthogonal Frequency Division Multiplexing (OFDM).

The total bandwidth in an OFDM system may be divided into narrowband frequency units which are called subcarriers. The number of subcarriers is equal to N which is size of the FFT/IFFT used in the system. Generally, the number of subcarriers used for data is less than N because some subcarriers at the edge of the frequency spectrum are reserved as guard subcarriers, and no information is transmitted on the guard subcarriers.

Turning now to FIG. 2 , Multiple Input Multiple Output (MIMO) schemes use multiple transmitting antennas and multiple receiving antennas in order to improve the capacity and reliability of a wireless communication channel. A MIMO system promises linear capacity with K where K is the minimum of number of transmitting antennas (M) at transmitter and receiving antennas (N) at receiver, i.e., K=min(M,N). FIG. 2 shows a simplified example of a 4×4 Multiple Input Multiple Output (MIMO) system. In this example, four different data streams Data Streams 1 to 4 are transmitted separately from the four transmit antennas Ant 1 T to Ant 4 T . The transmitted signals are received at four receiving antennas Ant 1 R to Ant 4 R . Spatial signal processing is performed on the received signals by spatial signal processor 200 in order to recover the four transmitted data streams. An example of spatial signal processing is V-BLAST which uses the successive interference cancellation (SIC) principle to recover the transmitted data streams. Other variants of MIMO schemes include schemes that perform some kind of space-time coding across the transmitting antennas (e.g. D-BLAST) and also beamforming schemes such as Spatial Division multiple Access (SDMA). One data stream corresponds to one data layer and therefore multiple data streams are corresponding to multiple data layers respectively.

In the current specifications of LTE (long term evolution) as defined in on page 26 of reference [6], codewords may be mapped to up to four data transmission layers in the MIMO transmission. The following is excerpt of section 6.3.3.2 of reference [6].

“6.3.3.2 Layer Mapping for Spatial Multiplexing

For spatial multiplexing, the layer mapping shall be done according to Table 6.3.3.2-1. The number of layers v is less than or equal to the number of antenna ports P used for transmission of the physical channel.”

Reference [6], on page 26, also provided Table 6.3.3.2-1 showing a mapping method between codewords and layers for the spatial multiplexing. In Table 6.3.3.2-1 as cited below, complex-valued modulation symbols d (q) (0), . . . d (q) (M symb (q) −1) for a code word q are mapped onto the data transmission layers x(i)=[x (0) (i) . . . x (v−1) (i)] T , where q refers the index of codewords, d (q) (i), i.e., d (q) (0), . . . , d (q) (M symb (q) −1) are complex-valued modulation symbols; M symb layer is the number of modulation symbols of each layer; x(i)=[x (0) (i) . . . x (v−1) (i)] T refers to data transmission layers where u refers to the total number of data transmission layers. Here, four data transmission layers respectively correspond to complex-value modulation symbols of two code words.

The feedback of channel quality information (CQI) in the case of two codeword MIMO transmission has been discussed in several 3GPP RAN1 contributions, such as references [1]-[3]. For example, reference [2] stated that the CQI may be fed back every N sub-frames where N is configured by the Node-B or network depending on the channel condition and/or deployment scenario. Per the agreement in reference [5], the CQI is defined per MIMO codeword with a maximum of two (2) CQIs corresponding to a maximum of two (2) codewords.

Reference [2], on pages 2-3, stated that:

“The CQI Definition Depends on the Transmission Rank:

For rank 1, only one (1) CQI is needed. For rank ≧2, two CQIs are needed, each associated with 1 codeword. The two CQIs can be:

1. Two full CQIs corresponding to the two CWs: CQI 1 and CQI 2 2. One full (base) CQI and one delta CQI: CQI base and CQI delta , CQI base can be defined either as the CQI of the first codeword. Then, CQI delta is simply the difference between CQI base and the CQI of the other CW.

CQI base =CQI 1

CQI delta =CQI 2 −CQI 1   (1)

The CQIs are computed from the channel, noise variance, and/or interference estimates. Once computed, the CQIs are quantized. Due to the inherent correlation between CQI 1 and CQI 2 , CQI delta requires fewer bits than CQI base since the dynamic range for CQI delta is smaller. Hence, employing delta CQI seems beneficial.”

The second approach of CQI base and CQI delta as cited above is the preferred approach in references [1]-[3], because the second approach may reduce the feedback overhead in the uplink by assigning fewer feedback bits for CQI delta than for CQI base .

In reference [4], however, the performance loss of this “CQI base +CQI delta ” could lead to potential performance loss in some scenarios because the dynamic range of the CQI delta may vary significantly in different configurations and channel situations. It was analyzed, in reference [4], that:

“Introducing the delta CQI scheme yields benefits in terms of reduced signaling overhead at least in UL. On the other hand, there will be situations, in which the second CQI deviates more from the first CQI than the delta metric can cover. In this case a loss in throughput is unavoidable. So, the reduction in signaling overhead has to be weighed against the loss of throughput. Recent analysis provided . . . analyses of the performance of the delta CQI scheme in terms of statistics. A significant variability between different configurations and channel situations has been found. The delta CQI values probability density function has a quite consistent characteristic, which implies significant throughput losses. The results of some important scenarios reveal a very limited compression potential.”

Noteworthy, as defined in reference [6], there are three preceding MIMO schemes that allow two-codeword transmission, namely zero CDD (cyclic delay diversity), small CDD and large delay CDD with spatial multiplexing. In large delay CDD systems, the CQI delta is always mapped a non-negative value of a delta SINR (signal to interference plus noise ratio) in dB indicating the benefits of successive interference cancellation (SIC) for the codeword that is decoded last; on the other hand, in small or zero delay CDD systems, CQI delta may be mapped to either a positive value or a negative value of a delta SINR in dB.

As one of embodiments of the present invention, configurable quantization methods for CQI delta are proposed based on conditions such as different antenna configurations and channel conditions. One example of configuration CQI quantization method is a configurable CQI step size used for CQI delta .

Aspects, features, and advantages of the invention are readily apparent from the following detailed description, simply by illustrating a number of particular embodiments and implementations, including the best mode contemplated for carrying out the invention. The invention is also capable of other and different embodiments, and its several details can be modified in various obvious respects, all without departing from the spirit and scope of the invention. Accordingly, the drawings and description are to be regarded as illustrative in nature, and not as restrictive. The invention is illustrated by way of example, and not by way of limitation, in the figures of the accompanying drawings.

In a two-codeword MIMO configuration, CQI base and CQI delta are obtained by quantizing the values measured on the two codewords in the MIMO transmission. Possible values measured on the codewords include effective SINR (signal to interference plus noise ratio), i.e., EESM (exponential effective signal SIR/SNR Mapping), modulation-constrained mutual information, and other related values. In the examples as shown in the present invention, effective SINR (or simply denoted as SINR) may be employed to illustrate the quantization process. The present invention however is not limited to the effective SINR but may be applied to other related values made on the codewords. SINR 1 and SINR 2 , which are observed at the user equipment (UE), are respectively denoted as values measured on two codewords. The SINRs may be either wide-band SINRs averaged over several subbands in the frequency domain, or may be SINRs averaged only over a single subband. The delta SINR between these two SINRs may be given by (SINR 2 -SINR 1 ). For example, the UE may quantize SINR 1 to achieve CQI base , and may quantize the difference (SINR 2 -SINR 1 ) in order to obtain CQI delta .

FIG. 3 shows an example of a procedure of obtaining a measurement of SINRs (signal to interference plus noise ratio) averaged over several subbands and obtaining the channel quality information (CQI) according to the obtained SINRs according to the principle of one embodiment of the present invention. As shown in FIG. 3 , SB 1 , SB 2 , . . . , and SB 10 are sampled subbands in the frequency domain. At step 200 , for example, the UE obtains two averaged SINRs (i.e., SINR 1 for one of the two codewords, and SINR 2 for the other of the two codewords) either over several subbands (e.g., SB 1 , SB 2 , . . . , and SB 10 ). At step 301 , the UE then may quantize the obtained SINR 1 in order to obtain CQI base ; and may quantize the delta SINR (i.e., (SINR 2 -SINR 1 )) in order to obtain CQI delta .

In the following examples illustrating the principles of the embodiments of the present invention, u S refers to a configurable step size employed by the quantization of CQI delta for the small or zero delay CDD preceding schemes; and u L refers to a configurable step size employed by the quantization of CQI delta for the large delay CDD precoding schemes.

In one embodiment of the present invention, configurable quantization of CQI delta is proposed. In one example, configurable step size u S for small/zero delay CDD precoding schemes and configurable step size u L for large delay CDD schemes for quantization of the CQI delta may be determined either according to the antenna configuration (such as antenna spacing) of the cell, or according to the channel condition of a given UE. Here, configurable offset o S may be defined for small/zero delay CDD precoding schemes and o L may be defined for large delay CDD schemes. One of the benefits of the configurable quantization is that the supported dynamic range of the CQI delta may be more flexible by employing the configurable step sizes and configurable offsets. For example, if a larger dynamic range is needed, the E-NodeB may configure a set of larger step sizes u S and u L ; on the other hand, if a smaller dynamic range is needed, the E-NodeB may configure a set of smaller step sizes u S and u L .

The value of step sizes u S and u L may have a predetermined relationship. For example, step size u S may be equal to step size u L (i.e., u S =u L ), or step size u S may be two times greater than step size u L (i.e., u S =2×u L ). The relationship between the values of step sizes however is not limited to the above stated example. In this case, E-NodeB only needs to configure one of two step sizes, and the other step size may be automatically set based on the configured one of two step sizes.

In one example of this embodiment, some or all of variables u S and u L may be configured in a cell-specific fashion, and are carried and transmitted by one of the E-NodeB (i.e., eNB) broadcast messages. These broadcast messages can be communicated to all the UEs within the cell on either Primary broadcast (PBCH) or Dynamic Broadcast (D-BCH) channels. In another example of this embodiment, some or all of variables u S and u L are configured in a UE-specific fashion, and are carried and transmitted by one of the higher-layer messages transmitted from E-NodeB to a UE semi-statically by using, for example, a radio resource control (RRC) message. In other words, the RRC message is transmitted from eNB to UE, to configure these two parameters in a semi-static fashion.

In one example of this embodiment, some or all of variables o S and o L may be configured in a cell-specific fashion, and are carried and transmitted by one of the E-NodeB (i.e., eNB) broadcast messages. These broadcast messages can be communicated to all the UEs within the cell on either Primary broadcast (PBCH) or Dynamic Broadcast (D-BCH) channels. In another example of this embodiment, some or all of variables o S and o L are configured in a UE-specific fashion, and are carried and transmitted by one of the higher-layer messages transmitted from E-NodeB to a UE semi-statically using, for example, a radio resource control (RRC) message.

At the UE side, the UE may receive these cell-specific or UE-specific parameters mentioned above, construct proper quantization tables for CQI delta , and then report CQI delta and CQI base to the E-NodeB. Here, the quantization table for CQI base is known.

FIG. 4 is flow charts illustrating processes of the quantization of CQI delta and CQI base according to the principle of one embodiment of the present invention. At step 401 , the UE measures the SINRs respectively for two codewords and thus obtaining SINR 1 and calculating delta SINR (i.e., (SINR 2 -SINR 1 )). At step 403 , the UE performs the quantization of CQI base by obtaining the CQI base based on the measured SINR 1 and a known quantization table defining a mapping method between the SINR 1 and CQI base . At step 405 , the UE receives the cell-specific or UE-specific parameters transmitted from the E-NodeB and configures a quantization table for CQI delta . At step 407 , the UE performs the quantization of CQI delta by calculating the CQI delta based on the obtained delta SINR and configured quantization table for CQI delta . At step 409 , the UE report CQI delta and CQI base to the E-NodeB. The operations at UE side are used to generate the input data as marked in FIG. 1 at transmitter side.

On the other hand, the E-NodeB receives CQI base and CQI delta from the UE feedback in the uplink channel, and the E-NodeB performs the reversed operation and looks up the quantization tables to figure out the (quantized) SINR 1 and Delta SINR (SINR 2 -SINR 1 ). As show in FIG. 4 , at step 501 , the E-NodeB receives CQI base and CQI delta transmitted from the UE. At step 502 and 503 , the E-NodeB respectively looks up the quantization tables for CQI base and CQI delta , therefore respectively determines the SINR 1 and delta SINR. At step 504 , the E-NodeB transmits the determined SINR 1 and delta SINR to the UE. The operations at eNodeB side are used to interpret the output data as marked in FIG. 1 at receiver side.

In order to fully define the mapping between CQI delta and the quantized delta SINR (SINR 2 -SINR 1 ) value, a quantization table defining the mapping between CQI delta and an intermediate variable denoted by c is firstly constructed. As an example, a 3-bit quantization table is given as Table 1. Table 1 shows uniform and non-uniform examples of mappings between CQI delta and intermediate variable c. Table 1 includes one uniform and two non-uniform quantization examples. In the non-uniform example A of the table, the step size in the variable c is smaller in the middle portion of Table 1 (step size of variable c is 1), and larger towards the two ending portions (step size of variable is 2). Note that other forms of non-uniform quantization may also exist. In the non-uniform example B of the table, the step size in the variable c increases from 1 to 2 while the signaled valued in CQI delta increases.

The final value (in dB) of Delta SINR (SINR 2 -SINR 1 ) may be given by equations (2) and (3) as follow:

for small-delay or zero-delay CDD preceding,

o S +c·u S (dB);   (2)

and for large-delay CDD preceding,

o L +c·u L (dB),   (3)

where o S and o L refer to configurable offsets respectively for small-delay or zero-delay CDD precoding and large-delay CDD precoding, and u S and u L refer to configurable steps respectively for small-delay or zero-delay CDD precoding and large-delay CDD precoding.

Therefore, a one-to-to quantization table may be constructed between the Delta SINR and CQI delta based on Table 1 and equations (2), (3).

In order to clearly illustrate the principle of constructing the quantization tables according to the embodiments of the present invention, several examples as follows are provided.

1. Large-delay Examples

On the assumption that parameters of o L =0 (dB) and u L =1 (dB) and a relatively small step size for one type of antenna/channel configuration (e.g. smaller antenna spacing), if a 3-bit uniform quantization (second column in Table 1) in the above table is used, then a CQI delta value of 010 indicates a Delta SINR of o L +c·u L =0+2*1=2 dB and a then CQI delta value of 110 indicates a Delta SINR of 0+6*1=dB. For the same example, given the same large-delay CDD preceding parameters, when a 3-bit non-uniform B (i.e., fourth column in Table 1) is used instead, then the then a CQI delta value of 010 indicates a Delta SINR of 0+2*1=2 dB and a then CQI delta value of 110 indicates a Delta SINR of 0+8*1=8 dB.

On the assumption of o L =0 (dB) and u L =1 (dB) and a relatively small step size for one type of antenna/channel configuration (e.g. smaller antenna spacing), when a 3-bit uniform quantization (i.e., second column in Table 1) is employed, Table 2 shows a uniform example of resulting mapping between CQI delta and Delta SINR based on the above assumptions.

In another large-delay CDD example with the parameters of o L =0 (dB) and u L =2 (dB) a slightly larger step size for another type of antenna/channel configuration (e.g. larger antenna spacing) is assumed, when a 3-bit uniform quantization (i.e., second column in Table 1) is employed, a CQI delta value 010 indicates a Delta SINR of o L +c·u L =0+2*2=4 dB and CQI delta value of 110 indicates a Delta SINR of 0+6*2=12 dB. Under the same assumptions, given the same large-delay CDD precoding parameters, when a 3-bit non-uniform B (i.e., fourth column in Table 1) is used instead, a CQI delta value of 010 indicates Delta SINR of 0+2*2=4 dB and CQI delta value of 110 indicates a Delta SINR of 0+8*2=16 dB.

Similarly, on the assumption that o L =0 (dB) and u L =2 (dB) and a three-bit non-uniform quantization (i.e., the third column of Table 1) is used, Table 3 may be constructed based on the above assumptions.

2. Zero/Small-delay Examples

In a zero/small-delay CDD preceding example with the parameters of o S =−7 (dB) and u S =2 (dB), a relatively small step size for one type of antenna/channel configuration (e.g. smaller antenna spacing) is assumed. When a 3-bit uniform quantization (i.e., second column in Table 1) is used, a CQI delta value of 010 indicates a Delta SINR of o S +c·u S −7+2*2=−3 dB and a then CQI delta value of 110 indicates a Delta SINR of −7+6*2=5 dB. Under the same assumptions, given the same large-delay CDD precoding parameters, when a 3-bit non-uniform A (i.e., the third column in Table 1) is used instead, a CQI delta value of 010 indicates a Delta SINR of −7+4*2=1 dB and CQI delta value of 110 indicates a Delta SINR of −7+9*2=11 dB.

In another zero/small-delay CDD precoding example with the parameters of o S =11 (dB) and u S =3 (dB), a relatively large step size for one type of antenna/channel configuration (e.g. larger antenna spacing) is assumed. When a 3-bit uniform quantization (i.e., second column in Table 1) in the above table is used, then a CQI delta value of 010 indicates a Delta SINR of o S +c·u S =−11+2*3=−5 dB and a then CQI delta value of 110 indicates a Delta SINR of −11+6*3=7 dB. Under the same assumptions, given the same large-delay CDD precoding parameters, if a 3-bit non-uniform A (third column in Table 1) is used instead, then the then a CQI delta value of 010 indicates a Delta SINR of −11+4*3=1 dB and a then CQI delta value of 110 indicates a Delta SINR of −11+9*3=16 dB.

Similarly, on the assumption that o S =−7 (dB) and u S =2 (dB) and a three-bit non-uniform quantization (i.e., the third column of Table 1) is used, Table 4 may be constructed based on the above assumptions.

The user equipment (UE) creates the quantization tables (e.g., Tables, 2, 3 or 4) based on equation (2) or (3) and Table 1, and calculates the CQI delta by using the Delta SINR (delta signal to Interference plus noise ratio) and the created quantization table (e.g., Tables, 2, 3 or 4). The E-NodeB utilizes the created quantization tables and the feedback of CQI delta in order to calculate the quantized Delta SINR based on the quantization tables.

Tables 2-4 shows examples of quatization tables defining mapping method of the Delta SINR and CQI delta . The present invention is not limited in these examples, however, on the contrary, is intended to cover various modifications and equivalent arrangements included within the spirit and scope of the appended claims, and equivalents thereof.