Dual operating mode electronic disabling device

This application is a continuation of and claims priority from U.S. patent application Ser. No. 10/364,164 filed Feb. 11, 2003 now U.S. Pat. No. 7,145,762 by Magne H. Nerheim.

The present invention relates to electronic disabling devices, and more particularly, to electronic disabling devices which generate a time-sequenced, shaped voltage waveform output signal.

The original stun gun was invented in the 1960's by Jack Cover. Such prior art stun guns incapacitated a target by delivering a sequence of high voltage pulses into the skin of a subject such that the current flow through the subject essentially “short-circuited” the target's neuromuscular system causing a stun effect in lower power systems and involuntary muscle contractions in more powerful systems. Stun guns, or electronic disabling devices, have been made in two primary configurations. A first stun gun design requires the user to establish direct contact between the first and second stun gun output electrodes and the target. A second stun gun design operates on a remote target by launching a pair of darts which typically incorporate barbed pointed ends. The darts either indirectly engage the clothing worn by a target or directly engage the target by causing the barbs to penetrate the target's skin. In most cases, a high impedance air gap exists between one or both of the first and second stun gun electrodes and the skin of the target because one or both of the electrodes contact the target's clothing rather than establishing a direct, low impedance contact point with the target's skin.

One of the most advanced existing stun guns incorporates the circuit concept illustrated in the FIG. 1 schematic diagram. Closing safety switch S 1 connects the battery power supply to a microprocessor circuit and places the stun gun in the “armed” and ready to fire configuration. Subsequent closure of the trigger switch S 2 causes the microprocessor to activate the power supply which generates a pulsed voltage output on the order of 2,000 volts which is coupled to charge an energy storage capacitor up to the 2,000 volt power supply output voltage. Spark gap GAP 1 periodically breaks down, causing a high current pulse through transformer T 1 which transforms the 2,000 volt input into a 50,000 volt output pulse.

Taser International of Scottsdale, Ariz., the assignee of the present invention, has for several years manufactured sophisticated stun guns of the type illustrated in the FIG. 1 block diagram designated as the Taser® Model M18 and Model M26 stun guns. High power stun guns such as these Taser International products typically incorporate an energy storage capacitor having a capacitance rating of from 0.2 microfarads at 2,000 volts on a light duty weapon up to 0.88 microfarads at 2,000 volts as used on the Taser M18 and M26 stun guns.

After the trigger switch S 2 is closed, the high voltage power supply begins charging the energy storage capacitor up to the 2,000 volt power supply peak output voltage. When the power supply output voltage reaches the 2,000 volt spark gap breakdown voltage, a spark is generated across the spark gap designated as GAP 1 . Ionization of the spark gap reduces the spark gap impedance from a near infinite impedance level to a near zero impedance and allows the energy storage capacitor to almost fully discharge through step up transformer T 1 . As the output voltage of the energy storage capacitor rapidly decreases from the original 2,000 volt level to a much lower level, the current flow through the spark gap decreases toward zero causing the spark gap to deionize and to resume its open circuit configuration with a near infinite impedance. This “re-opening” of the spark gap defines the end of the first 50,000 volt output pulse which is applied to output electrodes designated in FIG. 1 as “E 1 ” and “E 2 .” A typical stun gun of the type illustrated in the FIG. 1 circuit diagram produces from 5 to 20 pulses per second.

Because a stun gun designer must assume that a target may be wearing an item of clothing such as a leather or cloth jacket which functions to establish a 0.25 inch to 1.0 inch air gap between stun gun electrodes E 1 and E 2 and the target's skin, stun guns have been required to generate 50,000 volt output pulses because this extreme voltage level is capable of establishing an arc across the high impedance air gap which may be presented between the stun gun output electrodes E 1 and E 2 and the target's skin. As soon as this electrical arc has been established, the near infinite impedance across the air gap is promptly reduced to a very low impedance level which allows current to flow between the spaced apart stun gun output electrodes E 1 and E 2 and through the target's skin and intervening tissue regions. By generating a significant current flow within the target across the spaced apart stun gun output electrodes, the stun gun essentially short circuits the target's electromuscular control system and induces severe muscular contractions. With high power stun guns, such as the Taser M18 and M26 stun guns, the magnitude of the current flow across the spaced apart stun gun output electrodes causes numerous groups of skeletal muscles to rigidly contract. By causing high force level skeletal muscle contractions, the stun gun causes the target to lose its ability to maintain an erect, balanced posture. As a result, the target falls to the ground and is incapacitated.

The “M26” designation of the Taser stun gun reflects the fact that, when operated, the Taser M26 stun gun delivers 26 watts of output power as measured at the output capacitor. Due to the high voltage power supply inefficiencies, the battery input power is around 35 watts at a pulse rate of 15 pulses per second. Due to the requirement to generate a high voltage, high power output signal, the Taser M26 stun gun requires a relatively large and relatively heavy 8 AA cell battery pack. In addition, the M26 power generating solid state components, its energy storage capacitor, step up transformer and related parts must function either in a high current relatively high voltage mode (2,000 volts) or be able to withstand repeated exposure to 50,000 volt output pulses.

At somewhere around 50,000 volts, the M26 stun gun air gap between output electrodes E 1 and E 2 breaks down, the air is ionized, a blue electric arc forms between the electrodes and current begins flowing between electrodes E 1 and E 2 . As soon as stun gun output terminals E 1 and E 2 are presented with a relatively low impedance load instead of the high impedance air gap, the stun gun output voltage will drop to a significantly lower voltage level. For example, with a human target and with about a 10 inch probe to probe separation, the output voltage of a Taser Model M26 might drop from an initial high level of 50,000 thousand volts to a voltage on the order of about 5,000 volts. This rapid voltage drop phenomenon with even the most advanced conventional stun guns results because such stun guns are tuned to operate in only a single mode to consistently create an electrical arc across a very high, near infinite impedance air gap. Once the stun gun output electrodes actually form a direct low impedance circuit across the spark gap, the effective stun gun load impedance decreases to the target impedance typically a level on the order of 1,000 ohms or less. A typical human subject frequently presents a load impedance on the order of about 200 ohms.

Conventional stun guns have by necessity been designed to have the capability of causing voltage breakdown across a very high impedance air gap. As a result, such stun guns have been designed to produce a 50,000 to 60,000 volt output. Once the air gap has been ionized and the air gap impedance has been reduced to a very low level, the stun gun, which has by necessity been designed to have the capability of ionizing an air gap, must now continue operating in the same mode while delivering current flow or charge across the skin of a now very low impedance target. The resulting high power, high voltage stun gun circuit operates relatively inefficiently yielding low electro-muscular efficiency and with high battery power requirements.

Briefly stated, and in accord with one embodiment of the invention, an electronic disabling device includes first and second electrodes positioned to establish first and second spaced apart contact points on a target wherein a high impedance air gap may exist between at least one of the electrodes and the target. The electronic disabling device includes a power supply for generating a first high voltage, short duration output across the first and second electrodes during the first time interval to ionize the air within the air gap to thereby reduce the high impedance across the air gap to a lower impedance to enable current flow across the air gap at a lower voltage level and for subsequently generating a second lower voltage, longer duration output across the first and second electrodes during a second time interval to maintain the current flow across the first and second electrodes and between the first and second contact points on the target to enable the current flow through the target to cause involuntary muscle contractions to thereby immobilize the target.

The invention is pointed out with particularity in the appended claims. However, other objects and advantages together with the operation of the invention may be better understood by reference to the following detailed description taken in connection with the following illustrations, wherein:

FIG. 1 illustrates a high performance prior art stun gun circuit.

FIG. 2 represents a block diagram illustration of one embodiment of the present invention.

FIG. 3A represents a block diagram illustration of a first segment of the system block diagram illustrated in FIG. 2 which functions during a first time interval.

FIG. 3B represents a graph illustrating a generalized output voltage waveform of the circuit element shown in FIG. 3A .

FIG. 4A illustrates a second element of the FIG. 2 system block diagram which operates during a second time interval.

FIG. 4B represents a graph illustrating a generalized output voltage waveform for the FIG. 4A circuit element during the second time interval.

FIG. 5A illustrates a high impedance air gap which may exist between one of the electronic disabling device output electrodes and spaced apart locations on a target illustrated by the designations “E 3 ,”“E 4 ,” and an intervening load Z LOAD .

FIG. 5B illustrates the circuit elements shown in FIG. 5A after an electric spark has been created across electrodes E 1 and E 2 which produces an ionized, low impedance path across the air gap.

FIG. 5C represents a graph illustrating the high impedance to low impedance configuration charge across the air gap caused by transition from the FIG. 5A circuit configuration into the FIG. 5B (ionized) circuit configuration.

FIG. 6 illustrates a graphic representation of a plot of voltage versus time for the FIG. 2 circuit diagram.

FIG. 7 illustrates a pair of sequential output pulses corresponding to two of the output pulses of the type illustrated in FIG. 6 .

FIG. 8 illustrates a sequence of two output pulses.

FIG. 9 represents a block diagram illustration of a more complex version of the FIG. 2 circuit where the FIG. 9 circuit includes a third capacitor.

FIG. 10 represents a more detailed schematic diagram of the FIG. 9 circuit.

FIG. 11 represents a simplified block diagram of the FIG. 10 circuit showing components during time interval T 0 to T 1 .

FIGS. 12A and 12B represent timing diagrams illustrating the voltages across capacitor C 1 , C 2 and C 3 during time interval T 0 to T 1 .

FIG. 13 illustrates the operating configuration of the FIG. 11 circuit during the T 1 to T 2 time interval.

FIGS. 14A and 14B illustrate the voltages across capacitors C 1 , C 2 and C 3 during the T 1 to T 2 time interval.

FIG. 15 represents a schematic diagram of the active components of the FIG. 10 circuit during time interval T 2 to T 3 .

FIG. 16 illustrates the voltages across capacitors C 1 , C 2 and C 3 during time interval T 2 to T 3 .

FIG. 17 illustrates the voltage levels across GAP 2 and E 1 to E 2 during time interval T 2 to T 3 .

FIG. 18 represents a chart indicating the effective impedance level of GAP 1 and GAP 2 during the various time intervals relevant to the operation of the present invention.

FIG. 19 represents an alternative embodiment of the invention which includes only a pair of output capacitors C 1 and C 2 .

FIG. 20 represents another embodiment of the invention including an alternative output transformer designer having a single primary winding and a pair of secondary windings.

In order to better illustrate the advantages of the invention and its contributions to the art, a preferred embodiment of the invention will now be described in detail.

Referring now to FIG. 2 , an electronic disabling device for immobilizing a target according to the present invention includes a power supply, first and second energy storage capacitors, and switches S 1 and S 2 which operate as single pole, single throw switches and serve to selectively connect the two energy storage capacitors to down stream circuit elements. The first energy storage capacitor is selectively connected by switch S 1 to a voltage multiplier which is coupled to first and second stun gun output electrodes designated E 1 and E 2 . The first leads of the first and second energy storage capacitors are connected in parallel with the power supply output. The second leads of each capacitor are connected to ground to thereby establish an electrical connection with the grounded output electrode E 2 .

The stun gun trigger controls a switch controller which controls the timing and closure of switches S 1 and S 2 .

Referring now to FIGS. 3 through 8 and FIG. 12 , the power supply is activated at time T 0 . The energy storage capacitor charging takes place during time interval T 0 -T 1 as illustrated in FIGS. 12A and 12B .

At time T 1 , switch controller closes switch S 1 which couples the output of the first energy storage capacitor to the voltage multiplier. The FIG. 3B and FIG. 6 voltage versus time graphs illustrate that the voltage multiplier output rapidly builds from a zero voltage level to a level indicated in the FIG. 3B and FIG. 6 graphs as “V HIGH .”

In the hypothetical situation illustrated in FIG. 5A , a high impedance air gap exists between stun gun output electrode E 1 and target contact point E 3 . The FIG. 5A diagram illustrates the hypothetical situation where a direct contact (i.e., impedance E 2 -E 4 equals zero) has been established between stun gun electrical output terminal E 2 and the second spaced apart contact point E 4 on a human target. The E 1 to E 2 spacing on the target is assumed to equal on the order of 10 inches. The resistor symbol and the symbol Z LOAD represents the internal target resistance which is typically less than 1,000 ohms and approximates 200 ohms for a typical human target.

Application of the V HIGH voltage multiplied output across the E 1 to E 3 high impedance air gap forms an electrical arc having ionized air within the air gap. The FIG. 5C timing diagram illustrates that after a predetermined time during the T 1 to T 2 high voltage waveform output interval, the air gap impedance drops from a near infinite level to a near zero level. This second air gap configuration is illustrated in the FIG. 5B drawing.

Once this low impedance ionized path has been established by the short duration application of the V HIGH output signal which resulted from the discharge of the first energy storage capacitor through the voltage multiplier, the switch controller opens switch S 1 and closes switch S 2 to directly connect the second energy storage capacitor across the electronic disabling device output electrodes E 1 and E 2 . The circuit configuration for this second time interval is illustrated in the FIG. 4A block diagram. As illustrated in the FIG. 4B voltage waveform output diagram, the relatively low voltage V LOW derived from the second output capacitor is now directly connected across the stun gun output terminals E 1 and E 2 . Because the ionization of the air gap during time interval T 1 to T 2 dropped the air gap impedance to a low level application of the relatively low second capacitor voltage “V LOW ” across the E 1 to E 3 air gap during time interval T 2 to T 3 will allow the second energy storage capacitor to continue and maintain the previously initiated discharge across the arced-over air gap for a significant additional time interval. This continuing, lower voltage discharge of the second capacitor during the interval T 2 to T 3 transfers a substantial amount of target-incapacitating electrical charge through the target.

As illustrated in FIGS. 4B , 5 C, 6 and 8 , the continuing discharge of the second capacitor through the target will exhaust the charge stored in the capacitor and will ultimately cause the output voltage from the second capacitor to drop to a voltage level at which the ionization within the air gap will revert to the non-ionized, high impedance state causing cessation of current flow through the target.

In the FIG. 2 block diagram, the switch controller can be programmed to close switch S 1 for a predetermined period of time and then to close switch S 2 for a predetermined period of time to control the T 1 to T 2 first capacitor discharge interval and the T 2 to T 3 second capacitor discharge interval.

During the T 3 to T 4 interval, the power supply will be disabled to maintain a factory preset pulse repetition rate. As illustrated in the FIG. 8 timing diagram, this factory preset pulse repetition rate defines the overall T 0 to T 4 time interval. A timing control circuit potentially implemented by a microprocessor maintains switches S 1 and S 2 in the open condition during the T 3 to T 4 time interval and disables the power supply until the desired T 0 to T 4 time interval has been completed. At time T 0 , the power supply will be reactivated to recharge the first and second capacitors to the power supply output voltage.

Referring now to the FIG. 9 schematic diagram, the FIG. 2 circuit has been modified to include a third capacitor and a load diode (or resistor) connected as shown. The operation of this enhanced circuit diagram will be explained below in connection with FIG. 10 and the related more detailed schematic diagrams.

Referring now to the FIG. 10 electrical schematic diagram, the high voltage power supply generates an output current 11 which charges capacitors C 1 and C 3 in parallel. While the second terminal of capacitor C 2 is connected to ground, the second terminal of capacitor C 3 is connected to ground through a relatively low resistance load resistor R 1 or as illustrated in FIG. 9 by a diode. The first voltage output of the high voltage power supply is also connected to a 2,000 volt spark gap designated as GAP 1 and to the primary winding of an output transformer having a 1 to 25 primary to secondary winding step up ratio.

The second equal voltage output of the high voltage power supply is connected to one terminal of capacitor C 2 while the second capacitor terminal is connected to ground. The second power supply output terminal is also connected to a 3,000 volt spark gap designated GAP 2 . The second side of spark gap GAP 2 is connected in series with the secondary winding of transformer T 1 and to stun gun output terminal E 1 .

In the FIG. 10 circuit, closure of safety switch S 1 enables operation of the high voltage power supply and places the stun gun into a standby/ready-to-operate configuration. Closure of the trigger switch designated S 2 causes the microprocessor to send a control signal to the high voltage power supply which activates the high voltage power supply and causes it to initiate current flow 11 into capacitors C 1 and C 3 and current flow 12 into capacitor C 2 . This capacitor charging time interval will now be explained in connection with the simplified FIG. 11 block diagram and in connection with the FIG. 12A and FIG. 12B voltage versus time graphs.

During the T 0 to T 1 capacitor charging interval illustrated in FIG. 11 and 12 , capacitors C 1 , C 2 and C 3 begin charging from a zero voltage up to the 2,000 volt output generated by the high voltage power supply. Spark gaps GAP 1 and GAP 2 remain in the open, near infinite impedance configuration because only at the end of the T 0 to T 1 capacitor charging interval will the C 1 /C 2 capacitor output voltage approach the 2,000 volt breakdown rating of GAP 1 .

Referring now to FIGS. 13 and 14 , as the voltage on capacitors C 1 and C 2 reaches the 2,000 volt breakdown voltage of spark gap GAP 1 , a spark will be formed across the spark gap and the spark gap impedance will drop to a near zero level. This transition is indicated in the FIG. 14 timing diagrams as well as in the more simplified FIG. 3B and FIG. 6 timing diagrams. Beginning at time T 1 , capacitor C 1 will begin discharging through the primary winding of transformer T 1 which will rapidly ramp up the E 1 to E 2 secondary winding output voltage to negative 50,000 volts as shown in FIG. 14 B. FIG. 14A illustrates that the voltage across capacitor C 1 relatively slowly decreases from the original 2,000 volt level while the FIG. 14B timing diagram illustrates that the multiplied voltage on the secondary winding of transformer T 1 will rapidly build up during the time interval T 1 to T 2 to a voltage approaching minus 50,000 volts.

At the end of the T 2 time interval, the FIG. 10 circuit transitions into the second configuration where the 3,000 volt GAP 2 spark gap has been ionized into a near zero impedance level allowing capacitors C 2 and C 3 to discharge across stun gun output terminals E 1 and E 2 through the relatively low impedance load target. Because, as illustrated in the FIG. 16 timing diagram, the voltage across C 1 will have discharged to a near zero level as time approaches T 2 , the FIG. 15 simplification of the FIG. 10 circuit diagram which illustrates the circuit configuration during the T 2 to T 3 time interval shows that capacitor C 1 has effectively and functionally been taken out of the circuit. As illustrated by the FIG. 16 timing diagram, during the T 2 to T 3 time interval, the voltage across capacitors C 2 and C 3 decreases to zero as these capacitors discharge through the now low impedance (target only) load seen across output terminals E 1 and E 2 .

FIG. 17 represents another timing diagram illustrating the voltage across GAP 2 and the voltage across stun gun output terminals E 1 and E 2 during the T 2 to T 3 time interval.

In one preferred embodiment of the FIG. 10 circuit, capacitor C 1 , the discharge of which provides the relatively high energy level required to ionize the high impedance air gap between E 1 and E 3 , can be implemented with a capacitor rating of 0.14 microfarads and 2,000 volts. As previously discussed, capacitor C 1 operates only during time interval T 1 to T 2 which, in this preferred embodiment, approximates on the order of 1.5 microseconds in duration. Capacitors C 2 and C 3 in one preferred embodiment may be selected as 0.02 microfarad capacitors for a 2,000 volt power supply voltage and operate during the T 2 to T 3 time interval to generate the relatively low voltage output as illustrated in FIG. 4B to maintain the current flow through the now low impedance dart-to-target air gap during the T 2 to T 3 time interval as illustrated in FIG. 5C . In this particular preferred embodiment, the duration of the T 2 to T 3 time interval approximates 50 microseconds.

Due to many variables, the duration of the T 0 to T 1 time interval may change. For example, a fresh battery may shorten the T 0 to T 1 time interval in comparison to circuit operation with a partially discharged battery. Similarly, operation of the stun gun in cold weather which degrades battery capacity might also increase the T 0 to T 1 time interval.

Since it is highly desirable to operate stun guns with a fixed pulse repetition rate as illustrated in the FIG. 8 timing diagram, the circuit of the present invention provides a microprocessor-implemented digital pulse control interval designated as the T 3 to T 4 interval in FIG. 8 . As illustrated in the FIG. 10 block diagram, the microprocessor receives a feedback signal from the high voltage power supply via a feedback signal conditioning element which provides a circuit operating status signal to the microprocessor. The microprocessor is thus able to detect when time T 3 has been reached as illustrated in the FIG. 6 timing diagram and in the FIG. 8 timing diagram. Since the commencement time T 0 of the operating cycle is known, the microprocessor will maintain the high voltage power supply in a shut down or disabled operating mode from T 3 until the factory preset pulse repetition rate defined by the T 0 to T 4 time interval has been achieved. While the duration of the T 3 to T 4 time interval will vary, the microprocessor will maintain the T 0 to T 4 time interval constant.

The FIG. 18 table entitled “Gap On/Off Timing” represents a simplified summary of the configuration of GAP 1 and GAP 2 during the four relevant operating time intervals. The configuration “off” represents the high impedance, non-ionized spark gap state while the configuration “on” represents the ionized state where the spark gap breakdown voltage has been reached.

FIG. 19 represents a simplified block diagram of a circuit analogous to the FIG. 10 circuit except that the circuit has been simplified to include only capacitors C 1 and C 2 . The FIG. 19 circuit is capable of operating in a highly efficient or “tuned” dual mode configuration according to the teachings of the present invention.

FIG. 20 illustrates an alternative configuration for coupling capacitors C 1 and C 2 to the stun gun output electrodes E 1 and E 2 via an output transformer having a single primary winding and a center-tapped or two separate secondary windings. The step up ratio relative to each primary winding and each secondary winding represents a ratio of 1 to 12.5. This modified output transformer still accomplishes the objective of achieving a 1 to 25 step-up ratio for generating an approximate 50,000 volt signal with a 2,000 volt power supply rating. One advantage of this double secondary transformer configuration is that the maximum voltage applied to each secondary winding is reduced by 50%. Such reduced secondary winding operating potentials may be desired in certain conditions to achieve a higher output voltage with a given amount of transformer insulation or for placing less high voltage stress on the elements of the output transformer.

Substantial and impressive benefits may be achieved by using the electronic disabling device of the present invention which provides for dual mode operation to generate a time-sequenced, shaped voltage output waveform in comparison to the most advanced prior art stun gun represented by the Taser M26 stun gun as illustrated and described in connection with the FIG. 1 block diagram.

The Taser M26 stun gun utilizes a single energy storage capacitor having a 0.88 microfarad capacitance rating. When charged to 2,000 volts, that 0.88 microfarad energy storage capacitor stores and subsequently discharges 1.76 joules of energy during each output pulse. For a standard pulse repetition rate of 15 pulses per second with an output of 1.76 joules per discharge pulse, the Taser M26 stun gun requires around 35 watts of input power which, as explained above, must be provided by a large, relatively heavy battery power supply utilizing, 8 series-connected AA alkaline battery cells.

For one embodiment of the electronic disabling device of the present invention which generates a time-sequenced, shaped voltage output waveform and with a C 1 capacitor having a rating of 0.07 microfarads and a single capacitor C 2 with a capacitance of 0.01 microfarads (for a combined rating of 0.08 microfarads), each pulse repetition consumes only 0.16 joules of energy. With a pulse repetition rate of 15 pulses per second, the two capacitors consume battery power of only 2.4 watts at the capacitors (roughly 3.5 to 4 watts at the battery), a 90% reduction, compared to the 26 watts consumed by the state of the art Taser M26 stun gun. As a result, this particular configuration of the electronic disabling device of the present invention which generates a time-sequenced, shaped voltage output waveform can readily operate with only a single AA battery due to its 2.4 watt power consumption.

Because the electronic disabling device of the present invention generates a time-sequenced, shaped voltage output waveform as illustrated in the FIGS. 3B and FIG. 4B timing diagrams, the output waveform of this invention is tuned to most efficiently accommodate the two different load configurations presented: a high voltage output operating mode during the high impedance T 1 to T 2 first operating interval; and, a relatively low voltage output operating mode during the low impedance second T 2 to T 3 operating interval.

As illustrated in the FIG. 5C timing diagram and in the FlGS. 2 , 3 A and 4 A simplified schematic diagrams, the circuit of the present invention is selectively configured into a first operating configuration during the T 1 to T 2 time interval where a first capacitor operates in conjunction with a voltage multiplier to generate a very high voltage output signal sufficient to breakdown the high impedance target-related air gap as illustrated in FIG. 5A . Once that air gap has been transformed into a low impedance configuration as illustrated in the FIG. 5C timing diagram, the circuit is selectively reconfigured into the FIG. 3A second configuration where a second or a second and a third capacitor discharge a substantial amount of current through the now low impedance target load (typically 1,000 ohms or less) to thereby transfer a substantial amount of electrical charge through the target to cause massive disruption of the target's neurological control system to maximize target incapacitation.

Accordingly, the electronic disabling device of the present invention which generates a time-sequenced, shaped voltage output waveform is automatically tuned to operate in a first circuit configuration during a first time interval to generate an optimized waveform for attacking and eliminating the otherwise blocking high impedance air gap and is then retuned to subsequently operate in a second circuit configuration to operate during a second time interval at a second much lower optimized voltage level to efficiently maximize the incapacitation effect on the target's skeletal muscles. As a result, the target incapacitation capacity of the present invention is maximized while the stun gun power consumption is minimized.

As an additional benefit, the circuit elements operate at lower power levels and lower stress levels resulting in either more reliable circuit operation and can be packaged in a much more physically compact design. In a laboratory prototype embodiment of a stun gun incorporating the present invention, the prototype size in comparison to the size of present state of the art Taser M26 stun gun has been reduced by approximately 50% and the weight has been reduced by approximately 60%.

It will be apparent to those skilled in the art that the disclosed electronic disabling device for generating a time-sequenced, shaped voltage output waveform may be modified in numerous ways and may assume many embodiments other than the preferred forms specifically set out and described above. Accordingly, it is intended that the appended claims cover all such modifications of the invention which fall within the true spirit and scope of the invention.