Driving control circuit for light-emitting device

1. Field of the Invention

The present invention relates in general to a driving control circuit for a light-emitting device. In particular, the present invention relates to a circuit to control the range of a driving current of a light-emitting device.

2. Description of the Related Art

In the present driving circuit of the light-emitting device, the bias current and the modulated current are controlled separately. The modulated current is provided by a differential output stage. The bias current is provided by a circuit source.

FIG. 1 is a circuit diagram of a conventional driving control circuit for a light-emitting device. In FIG. 1, the conventional driving control circuit drives a laser diode LD 100 . This circuit includes a pair of input terminals 100 and 101 , and a differential output circuit 102 to be applied with a digital data signal to drive the laser diode LD 100 , a current source circuit 105 for supplying a constant current I 101 as a driving current to the laser diode LD 100 through the differential output circuit 102 , and a current source circuit 106 for supplying a constant current I 102 as a dc bias current to the laser diode LD 100 .

The differential output circuit 102 is formed by n-channel MOS transistors Q 101 and Q 102 whose sources are coupled together, such as by a source-coupled pair of MOS transistors Q 101 and Q 102 . The digital data signal is applied across the non-inverted input terminal 100 and the inverted input terminal 101 . The terminal 100 is connected to a gate of the MOS transistor Q 102 . The terminal 101 is connected to a gate of the MOS transistor Q 101 . A drain of the transistor Q 101 is connected to one end of a load resistor R 101 . The other end of the resistor R 101 is applied with a power supply voltage V DD . A drain of the transistor Q 102 , which serves as an output terminal of the conventional driving control circuit, is connected to the cathode of the laser diode LD 100 . The anode of the laser diode LD 100 is applied with the power supply voltage V DD .

The current source circuit 105 is formed by n-channel MOS transistors Q 103 and Q 104 serving as a current mirror, and a reference current source 103 for supplying a constant reference current I ref1 to the transistor Q 104 . A drain of the transistor Q 103 is connected to the coupled sources of the transistors Q 101 and Q 102 . A source of the transistor Q 103 is connected to the ground. A drain and a gate of the transistor Q 104 are connected in common to a gate of the transistor Q 103 . A source of the transistor Q 104 are connected to the ground. The commonly connected drain and gate of the transistor Q 104 are connected to one end of the reference current source 103 . The other end of the reference current source 103 is applied with the power supply voltage V DD .

The current source circuit 106 is formed by n-channel MOS transistors Q 105 and Q 106 serving as a current mirror, and a reference current source 104 for supplying a constant reference current I ref2 to the transistor Q 106 . A drain of the transistor Q 105 is connected to the drain of the cathode of the laser diode LD 100 , i.e., the output terminal of the conventional driving control circuit of FIG. 1. A source of the transistor Q 105 is connected to the ground. A drain and a gate of the transistor Q 106 is connected in common to a gate of the transistor Q 105 . A source of the transistor Q 106 is connected to the ground. The commonly connected drain and gate of the transistor Q 106 are connected to one end of the reference current source 104 . The other end of the reference current source 104 is applied with the power supply voltage V DD .

The above-described conventional driving control circuit of FIG. 1 has the following problems:

The first problem is that the current consumption of the circuit of FIG. 1 is large, because the dc bias current I 102 is always consumed during operation irrespective of the existence and absence of light emission and because the driving current I 101 .

Second, the work voltage in the output terminal is limited because two transmitters are series in the differential output stage. Therefore, the circuit of FIG. 1 does not work when the output work voltage is lower than V DD . The efficiency of the current is reduced and the application of the circuit becomes more complex.

An object of the present invention is to provide a driving control circuit for a light-emitting device that has better efficiency and is able to increase the work voltage in the output terminal.

Another object of the present invention is to provide a driving control circuit for a light-emitting device that automatically adjusts a gate voltage of the output transistor according to a predetermined bias voltage, and a modulated current to control the gate voltage precisely, thereby enabling a decrease in the power consumption and an increase in the range of the work voltage in the output terminal.

The inventive circuit comprises an adjustable gain circuit, a current output circuit, and a level control circuit. The adjustable gain circuit receives a digital signal and generates an output voltage controlled by a first control signal and a second control signal. The current output circuit comprises a first transistor. A gate of the first transistor is coupled to the adjustable gain circuit. The adjustable gain circuit adjusts a range of the gate voltage to generate the high-speed modulated current. The level control circuit sets the voltages of the first control signal and the second control signal.

The level control circuit comprises a duplicate circuit, a first negative feedback current and a second negative feedback current. The duplicate circuit receives a high level signal and a low level signal and generates a first output current and a second output current. The first negative feedback current sets the first current equal to a first predetermined current and outputs a voltage to set a voltage of the first control signal. The second negative feedback current sets the second current equal to a second predetermined current and outputs a voltage to set a voltage of the second control signal. The high level signal raises the gate voltage of the first transistor above a high level voltage. The low level signal lowers the gate voltage of the first transistor below a low level voltage. The adjustable range of the gate voltage is between the high level voltage and the low level voltage.

Furthermore, the invention also provides another driving control circuit for a light-emitting device to generate a high-speed modulated current to drive the light-emitting device. The circuit comprises an adjustable gain circuit, a current output circuit and a level control circuit. The adjustable gain circuit receives a digital signal and generates an output voltage controlled by a first control signal and a second control signal. The current output circuit comprises a first transistor. A gate of the first transistor is coupled to the adjustable gain circuit. The adjustable gain circuit adjusts a range of the gate voltage to generate the high-speed modulated current. The level control circuit sets the voltages of the first control signal and the second control signal.

The level control circuit comprises a level detect circuit, a first negative feedback current and a second negative feedback current. The level detect circuit is coupled to the adjustable gain circuit and generates a first output current and a second output current. The first negative feedback current sets the first current equal to a first predetermined current and outputs a voltage to set a voltage of the first control signal. The second negative feedback current sets the second current equal to a second predetermined current and outputs a voltage to set a voltage of the second control signal. The adjustable range of the gate voltage is between a high level voltage and a low level voltage.

The present invention can be more fully understood by reading the subsequent detailed description in conjunction with the examples and references made to the accompanying drawings, wherein:

FIG. 1 is a circuit diagram of a conventional driving control circuit for a light-emitting device;

FIG. 2A is a schematic diagram of a driving control circuit for a light-emitting device according to the invention;

FIG. 2B is a graph showing the relation between a voltage of a gate of an output transmitter and two predetermine currents;

FIG. 3A is a schematic diagram of a driving control circuit for a light-emitting device according to a first embodiment of the invention;

FIG. 3B is a graph showing the relation between input signals and output voltages of the adjustable gain circuit and the adjustable circuit of FIG. 3A;

FIG. 4 is a circuit diagram of a driving control circuit for a light-emitting device according to the first embodiment of the invention;

FIG. 5 A and FIG. 5B are diagrams of output circuits which are produced by simulating different predetermined circuits according to the first embodiment of the invention; and

FIG. 6 is a schematic diagram of a driving control circuit for a light-emitting device according to a second embodiment of the invention.

FIG. 2A is a schematic diagram of a driving control circuit for a light-emitting device according to the invention. A digital signal 203 is input to a control circuit 200 . The output of the control circuit 200 is connected to a gate of an output transmitter Q 201 . A drain of the output transistor Q 201 , which serves as an output terminal of the conventional driver circuit, is connected to a cathode of a light-emitting device LD 202 . The anode of the light-emitting device LD 202 is applied with a power supply voltage V CC . The control circuit 200 controls the gate voltage Vg of the output transistor Q 201 precisely. The control circuit 200 automatically adjusts the gate voltage Vg according to predetermined currents IL and IH to generate a high-speed modulated current Iout to drive the light-emitting device LD 202 , thereby enabling a decrease in the power consumption and an increase in the range of the work voltage in the output terminal. The predetermined current IL is a bias current of the light-emitting device LD 202 . The predetermined current IH is a sum current of the bias current and a high-speed modulated current of the light-emitting device LD 202 .

FIG. 2B is a graph showing the relation between a voltage of a gate of an output transmitter and two predetermine currents. The cross axis is the gate voltage Vg. The vertical axis is the high-speed modulated current Iout. The point A in the FIG. 2B is the predetermined current IH corresponding to the high level of the gate voltage VH. The point B in the FIG. 2B is the predetermined current IL corresponding to the low level of the gate voltage VL.

FIG. 3A shows a schematic diagram of a driving control circuit for a light-emitting device according to a first embodiment of the invention. A digital signal 303 is input to a control circuit 300 . The output of the control circuit 200 is connected to a gate of an output transmitter Q 301 . A drain of the output transistor Q 301 , which serves as an output terminal of the conventional driver circuit, is connected to a cathode of a light-emitting device LD 302 . The anode of the light-emitting device LD 202 is applied with a power supply voltage V CC .

The control circuit 300 comprises an adjustable gain circuit 304 and a level control circuit 306 . The adjustable gain circuit 304 receives the digital signal 303 and generates an output voltage controlled by a VL control signal and a VH control signal. A high level signal HI and a low level signal LO of the digital signal are input to the level control circuit 306 to set the VL control signal and the VH control signal.

The level control circuit 306 comprises an adjustable circuit 308 , a transistor Q 312 , two comparison circuits 310 and 320 and two current sources 314 and 324 . The adjustable circuit 308 comprises two duplicate adjustable gain circuit 308 a and 308 b . Each structure of the duplicate adjustable gain circuits is the same as the adjustable gain circuit 304 . Therefore, the duplicate adjustable gain circuits 308 a and 308 b can simulate the output of the adjustable gain circuit 304 . The duplicate adjustable gain circuit 308 a receives the high level signal HI and generates a high voltage VH 1 to output. The duplicate adjustable gain circuit 308 b receives the low level signal LO and generates a low voltage VL 1 to output. The high voltage VH 1 is input to a gate of a transistor Q 312 . A drain of the transistor Q 312 outputs an output current IH 1 . The output current IH 1 is input to the comparison circuit 310 . The comparison circuit 310 makes the output current IH 1 equal to a predetermined current IH provided the current source 314 . The VH control signal is set by an output from the output terminal of the comparison circuit 310 . The low voltage VL 1 is input to a gate of a transistor Q 322 . A drain of the transistor Q 322 outputs an output current IL 1 . The output current IL 1 is input to the comparison circuit 320 . The comparison circuit 320 makes the output current IL 1 equal to a predetermined current IL provided by the current source 324 . The VL control signal is set by an output from the output terminal of the comparison circuit 320 .

The control circuit 300 controls the gate voltage Vg of the output transistor Q 301 precisely. The control circuit 300 automatically adjusts the gate voltage Vg according to the predetermined currents IL provided by the current source 324 and the predetermined currents IH provided by the current source 314 to generate a high-speed modulated current Iout to drive the light-emitting device LD 302 , thereby enabling a decrease in the power consumption and an increase in the range of the work voltage in the output terminal. The predetermined current IL is a bias current of the light-emitting device LD 302 . The predetermined current IH is a sum current of the bias current and a high-speed modulated current of the light-emitting device LD 302 .

FIG. 3B shows a graph showing the relation between input signals and output voltages of the adjustable gain circuit 304 and the adjustable circuit 308 . The cross axis is the input voltage Vi of the adjustable gain circuit 304 . The vertical axis is the output voltage Vo of the adjustable gain circuit 304 . The high level signal HI raises the output voltage Vo above a high level voltage VH. The low level signal LO lowers the output voltage Vo below a low level voltage VL. The high level voltage VH approximates a high level of the gate voltage of the transmitter Q 301 . The low level voltage VL also approximates a low level of the gate voltage of the transmitter Q 301 .

FIG. 4 is a circuit diagram of a driving control circuit for a light-emitting device according to the first embodiment of the invention. As shown in FIG. 4, the driving control circuit for the light-emitting device generates a high-speed modulated current Iout to drive the light-emitting device LD 401 . The driving control circuit for the light-emitting device comprises an adjustable gain circuit 404 , a level buffer circuit 406 , a current output circuit 408 and a level control circuit 410 . In the embodiment, a pair of differential signals is input to the adjustable gain circuit 404 . The differential signals comprise a first digital signal 402 and a second digital signal 403 . The second digital signal 402 is an inverse signal of the first digital signal 402 . An output voltage of the adjustable gain circuit 404 is controlled by a VL control signal VC 1 and a VH control signal VC 2 . The level buffer circuit 406 transforms the level of the output voltage from the adjustable gain circuit 404 . The current output circuit 408 comprises a transistor Q 501 . A gate of the transistor Q 501 is connected to the level buffer circuit 406 , then to the adjustable gain circuit 404 . The adjustable gain circuit 404 adjusts a range of the gate voltage of the transistor Q 501 to generate the high-speed modulated current Iout. The level control circuit 410 sets the VL control signal VC 1 and the VH control signal VC 2 .

The adjustable gain circuit 404 comprises transistors Q 502 ˜Q 506 . The first digital signal 402 is input to a gate of the transistor Q 502 . The second digital signal 403 is input to a gate of the transistor Q 503 . The VL control signal VC 2 is input to a gate of the transistor Q 504 and a gate of the transistor Q 505 . The VH control signal VC 1 is input to a gate of the transistor Q 506 . A connection point of a drain of the transistor Q 503 and a drain of the transistor Q 505 is an output terminal of the adjustable gain circuit 404 .

The level control circuit comprises a duplicate circuit 412 , a first negative feedback current 414 and a second negative feedback current 416 . A high level signal HI and a low level signal LO are input to the duplicate circuit 416 . The duplicate circuit 416 generates an output current IH 1 and an output current IL 1 . The first negative feedback current 414 sets the output current IH 1 equal to a first predetermined current IH provided by a current source 415 . The first negative feedback current 414 outputs a voltage to set the VH control signal VC 1 . The second negative feedback current 416 sets the output current IL 1 equal to a first predetermined current IL provided by a current source 417 . The second negative feedback current 416 outputs a voltage to set the VL control signal VC 2 . The high level signal HI is an input signal that makes the gate voltage of the transistor Q 501 over than the range. The low level signal Lo is an input signal that makes the gate voltage of the transistor Q 501 under than the range. In application, to simplify the circuit, the high level signal HI is a power supply voltage V cc and the low level signal LO is a ground voltage gnd.

The duplicate circuit 412 comprises an adjustable circuit 418 , a first level buffer circuit 420 , a first current output circuit 422 , a second level buffer circuit 424 and a second current output circuit 426 . The structure of the duplicate adjustable gain circuit 418 is the same as the adjustable gain circuit 404 . The high level signal HI and the low level signal LO are input to the adjustable gain circuit 418 . The adjustable gain circuit 418 generates output voltages VO 1 and VO 2 . The structure of the first level buffer circuit 420 is the same as the level buffer circuit 406 , but the first level buffer circuit 420 transforms the level of the output voltage VO 1 from the adjustable circuit 418 . The structure of the first current output circuit 422 is the same as the current output circuit 408 . The first current output circuit 422 comprises a transistor Q 507 . A gate of the transistor Q 507 is connected to the first level buffer circuit 420 . The output current IH 1 is output from a drain of the transistor Q 507 . The structure of the second level buffer circuit 424 is the same as the level buffer circuit 406 , but the second level buffer circuit 424 transforms the level of the output voltage VO 2 from the adjustable circuit 418 . The structure of the second current output circuit 426 is the same as the current output circuit 408 . The second current output circuit 426 comprises a transistor Q 508 . A gate of the transistor Q 508 is connected to the second level buffer circuit 424 . The output current IL 1 is output from a drain of the transistor Q 508 .

The first negative feedback current 414 comprises a first comparison circuit 428 for comparing the output circuit IH 1 and the predetermined current IH. The second negative feedback current 416 comprises a second comparison circuit 430 for comparing the output circuit IL 1 and the predetermined current IL. The predetermined current IL is a bias current of the light-emitting device LD 401 . The predetermined current IH is a sum current of the bias current and a high-speed modulated current of the light-emitting device LD 401 .

FIG. 5 A and FIG. 5B are diagrams of output circuits produced by simulating different predetermined circuits according to the first embodiment of the invention. The cross axis is time. The vertical axis is current. The unit of the current is mA. As shown in FIG. 5A, the signal waveform 52 is the output of the driving control circuit according to the first embodiment of the invention, i.e. the high-speed modulated current Iout of the light-emitting device, when the predetermined circuit IH=40 mA and IL=15 mA. As shown in FIG. 5B, the signal waveform 54 is the output of the driving control circuit according to the first embodiment of the invention, i.e. the high-speed modulated current Iout of the light-emitting device, when the predetermined circuit IH=10 mA and IL=3 mA.

FIG. 6 shows a schematic diagram of a driving control circuit for a light-emitting device according to a second embodiment of the invention. The first embodiment in FIG. 3A is basically the same as the second embodiment in FIG. 6, with the difference that the adjustable circuit 308 in the first embodiment is replaced by a level detector 608 in the second embodiment. Thus, instead of inputting the high level signal HI, the low level signal LO and the output voltage of the adjustable gain circuit into the adjustable circuit 308 , it only requires input of the output voltage of the adjustable gain circuit to the level detector 608 .

As shown in FIG. 6, a digital signal 603 is input to the control circuit 600 . The output of the control circuit 600 is connected to a gate of an output transmitter Q 601 . A drain of the output transistor Q 601 , which serves as an output terminal of the conventional driver circuit, is connected to a cathode of a light-emitting device LD 602 . The anode of the light-emitting device LD 202 is applied with a power supply voltage V CC .

The control circuit 600 comprises an adjustable gain circuit 604 and a level control circuit 606 . The adjustable gain circuit 604 receives the digital signal 603 and generates the output voltage controlled by a VL control signal and a VH control signal. A high level signal HI and a low level signal LO of the digital signal is input to the level control circuit 606 to set the VL control signal and the VH control signal.

The level control circuit 606 comprises the level detector 608 , a transistor 6312 , two comparison circuits 610 and 620 and two current sources 614 and 624 . The output voltage of the adjustable gain circuit 604 is input to the level detector 608 . After detecting levels of the output voltage, the level detector 608 generates a high voltage VH 1 and a low voltage VL 1 to output. The high voltage VH 1 is input to a gate of a transistor Q 612 . A drain of the transistor Q 612 outputs an output current IH 1 . The output current IH 1 is input to the comparison circuit 610 . The comparison circuit 610 makes the output current IH 1 equal to a predetermined current IH provided the current source 614 . The VH control signal is set by an output from the output terminal of the comparison circuit 610 . The low voltage VL 1 is input to a gate of a transistor Q 622 . A drain of the transistor Q 622 outputs an output current IL 1 . The output current IL 1 is input to the comparison circuit 620 . The comparison circuit 620 makes the output current IL 1 equal to a predetermined current IL provided by the current source 624 . The VL control signal is set by an output from the output terminal of the comparison circuit 620 .

The control circuit 600 controls the gate voltage Vg of the output transistor Q 601 precisely. The control circuit 600 automatically adjusts the gate voltage Vg according to the predetermined currents IL provided by the current source 624 and the predetermined currents IH provided by the current source 614 to generate a high-speed modulated current Iout to drive the light-emitting device LD 602 , thereby enabling a decrease in the power consumption and an increase in the range of the work voltage in the output terminal. The predetermined current IL is a bias current of the light-emitting device LD 602 . The predetermined current IH is a sum current of the bias current and a high-speed modulated current of the light-emitting device LD 602 .

Finally, while the invention has been described by way of example and in terms of the preferred embodiment, it is to be understood that the invention is not limited to the disclosed embodiments. On the contrary, it is intended to cover various modifications and similar arrangements as would be apparent to those skilled in the art. Thus, the scope of the appended claims should be accorded the broadest interpretation so as to encompass all such modifications and similar arrangements.