Frequency-switching oscillator and electronic device using the same

This application is a divisional of application Ser. No. 09/518,819 filed Mar. 3, 2000, now U.S. Pat. No. 6,384,693.

1. Field of the Invention

The present invention relates to a frequency-switching oscillator and an electronic device using the same, and more particularly relates to a frequency-switching oscillator for switching oscillation frequencies by switching the feedback capacitance of a resonance system or an amplification system, and to an electronic device using the same.

2. Description of the Related Art

Generally, an oscillator has a resonance system and an amplification system, and the relationship between the resonance system and the amplification system must satisfy conditions for oscillation in order for the oscillator to oscillate. The conditions for oscillation are that the impedance of the amplification system has a negative resistance to compensate the impedance loss of the resonance system. In addition, the imaginary part of the impedance of the resonance system and the imaginary part of the impedance of the amplification system must have reverse signs, and the same absolute values. Further, in the Colpitts oscillator used in the following explanation, it is required for the impedance of the resonance system to be inductive to satisfy a condition of oscillation.

FIG. 8 is a Smith chart showing frequency characteristics of the impedance of the resonance system and the amplification system. The top half portion of the circle shows that the impedance is inductive, and the bottom half portion of the circle shows that the impedance is capacitive. The inner portion of the circle shows that the impedance is a resistance, and the outer portion of the circle shows that the impedance is a negative resistance. Then, the point where the impedance on the right end of the circle is extremely high is called a resonance point. The phase q of the impedance is shown counterclockwise from the right end of the circle from 0 degrees to 360 degrees. In FIG. 8, the solid lines show the frequency characteristics of the impedance. The impedance at a higher frequency is shown as it moves clockwise from an impedance at a certain frequency on the solid line. For example, frequency fb is higher than frequency fa. Furthermore, the impedance at frequency fa and frequency fb is a resistance, and the impedance at frequency fc is a negative resistance. Moreover, the difference in phase of the impedance at frequency fa and at frequency fb is approximately 340 degrees. As an example of phase difference and a resonance point, in the Smith chart, the phase difference between an impedance at a given frequency on the solid line and an impedance at a frequency two cycles to the right from that impedance is 720 degrees, in which case the resonance point is passed twice.

A frequency-switching oscillator is an oscillator which outputs two or more oscillation frequency signals, and conditions for oscillation must be satisfied at each of the different oscillation frequencies. Conventional frequency-switching oscillators comprise a switch element as switching member in the resonance system, and output two or more oscillation frequencies, satisfying the conditions for oscillation at each of the different oscillation frequencies, by switching the state of the switch element.

FIG. 9 shows a conventional frequency-switching oscillator 11 . The basic concept of the frequency-switching oscillator 11 shown in FIG. 9 is disclosed in Japanese Unexamined Patent Publication No. 9-307354.

In FIG. 9, the frequency-switching oscillator 11 is a Colpitts oscillator with oscillation frequencies f 11 and f 12 , and is provided with a resonance system 12 and an amplification system 13 being connected.

Firstly, the resonance system 12 has a coil L 12 , a coil L 13 , a coil L 14 , a diode D 11 , a capacitor C 13 , and a switching voltage input terminal a 15 . These elements are important in determining the impedance of the resonance system. One end of the coil L 12 is connected via a resonance output terminal a 12 to the amplification system 13 , and the other end is connected to the anode of the diode D 11 and one end of the coil L 14 . The other end of the coil L 14 is connected to the switching voltage input terminal a 15 , and is grounded via the capacitor C 13 . The cathode of the diode D 11 is grounded via the coil L 13 .

Then, when a switching voltage is applied to the switching voltage input terminal a 15 , the diode D 11 becomes conductive, thereby operating as a resonator which is termination-grounded by the coil L 12 and the coil L 13 ; when no switching voltage is applied, the diode D 11 becomes nonconductive, thereby operating as a resonator which is termination-opened by the coil L 12 . Here, the coil L 14 is a choke coil, and C 13 is a ground capacitor.

The frequency-switching oscillator 11 is a voltage-controlled oscillator, having a coil L 11 , a capacitor C 11 , a capacitor C 12 , a variable-capacitance diode VD 11 , and a control voltage input terminal, which are all corresponding to the voltage-controlled portion. The capacitance value of the variable-capacitance diode VD 11 is adjusted by a control voltage inputted from the control voltage input terminal via the coil L 11 which is a choke coil. The variable-capacitance diode VD 11 is connected via the capacitor C 12 to one end of the coil L 12 .

The impedance of the resonance system 12 of such a frequency-switching oscillator 11 is the impedance seen from the resonance output terminal a 12 of the resonance system 12 when the frequency-switching oscillator 11 is separated into the resonance system 12 and the amplification system 13 .

FIGS. 10A and 10B show frequency characteristics of the impedance of the resonance system 12 using a Smith chart. FIG. 10A shows the impedance when the diode D 11 is conductive, and FIG. 10B shows the impedance when the diode D 11 is nonconductive. Furthermore, the impedances at oscillation frequencies f 11 and f 12 are shown by reference numerals f 11 and f 12 .

As shown in FIGS. 10A and 10B, when the diode D 11 is conductive or nonconductive as a result of application of a switching voltage to the switching voltage input terminal a 15 , the impedance of the resonance system 12 greatly changes. FIG. 10A shows the case when a switching voltage is applied to the switching voltage input terminal a 15 , and the impedance of the resonance system 12 is inductive at f 11 and f 12 . Then, FIG. 10B shows a case when no switching voltage is applied, whereby the impedance of the resonance system 12 is capacitive at f 11 , and inductive at f 12 .

Furthermore, in FIG. 9, in the amplification system 13 , a transistor TR 11 is an amplification element. The collector of the transistor TR 11 is connected to a power supply input terminal a 14 , one end of a capacitor C 19 , and one end of a capacitor C 17 , and also is connected via a capacitor C 14 to the resonance system 12 . The base of the transistor TR 11 is connected to the other end of the capacitor C 17 , and is grounded via the capacitor C 15 . In addition, a power supply voltage voltage-divided by a resistance R 11 and a resistance R 12 is input to the base of the transistor TR 11 . The emitter of transistor TR 11 is connected to the other end of the capacitor C 19 , is grounded via a capacitor C 16 and a resistance R 13 , and is connected via a capacitor C 18 to an oscillation output terminal a 16 . Thus, the amplification system 13 has no switching member, and the frequency characteristics of the impedance of the amplification system 13 are not switched.

The impedance of amplification system 13 is the impedance seen from the oscillation input terminal a 13 when the frequency-switching oscillator 11 is separated into the resonance system 12 and the amplification system 13 . FIG. 11 shows the impedance of the amplification system 13 , and the impedance at the oscillation frequencies f 11 and f 12 is shown by reference numerals f 11 and f 12 . In FIG. 11, the impedance of the amplification system 13 is a negative resistance at the oscillation frequencies f 11 and f 12 .

Here, the following points can be understood from the impedances of the resonance system 12 and the amplification system 13 . Firstly, at the oscillation frequencies f 11 and f 12 shown in FIG. 10A in the resonance system, the impedance is inductive, and satisfies the conditions for oscillation. Next, the impedances at the oscillation frequencies f 11 and f 12 of FIG. 11 satisfy the conditions for oscillation by having sufficient negative resistance to compensate the impedance at the oscillation frequencies f 11 and f 12 shown in FIG. 10 A. The impedance at the oscillation frequency f 11 of FIG. 11 in the amplification system has sufficient negative resistance to satisfy the conditions for oscillation. However, the impedance at the oscillation frequency f 12 of FIG. 11 does not have sufficient negative resistance and therefore does not satisfy the conditions for oscillation. For this reason, when the diode D 11 is conductive, i.e. the switch voltage is applied, the conditions for oscillation are only satisfied at the oscillation frequency f 11 .

The impedance at the oscillation frequency f 11 shown in FIG. 10B is capacitive, and does not satisfy the conditions for oscillation. In contrast, the impedance at the oscillation frequency f 12 is inductive and satisfies the oscillation conditions. Next, the impedance at the oscillation frequency f 12 shown in FIG. 11 has sufficient negative resistance to supplement the impedance at the oscillation frequency f 12 shown in FIG. 10B, and satisfies the conditions for oscillation. For this reason, when the diode D 11 is nonconductive, the conditions for oscillation are only satisfied at the oscillation frequency f 12 .

Therefore, when a switching voltage is applied to the switching voltage input terminal a 15 , the oscillation signal s 11 of the frequency-switching oscillator 11 is the oscillation frequency f 11 . When a switching voltage is not applied to the switching voltage input terminal a 15 , the oscillation signal s 11 switches to the oscillation frequency f 12 .

According to the conventional frequency-switching oscillator 11 , loss resulting from the internal resistance of the diode D 11 increases the loss of the resonance system 12 , and causes problems such as a drop in the output level, deterioration in the carrier to noise ratio, or the like.

Furthermore, according to the conventional frequency-switching oscillator 11 , when it is desired to widen the switch width between the oscillation frequency f 11 and the oscillation frequency f 12 , it can be designed to satisfy the conditions for oscillation by the switching member D 11 provided in the resonance system 12 . However, since the amplification system 13 does not include a switching member, the range of frequencies in which the impedance of the amplification system 13 has a sufficiently large negative resistance is narrow, making it impossible for the amplification system 13 to satisfy the conditions for oscillation. As a consequence, the conventional frequency-switching oscillator 11 , in which the switching member D 11 is provided in only the resonance system 12 , has a disadvantage that it is difficult to set a large switch width between the oscillation frequencies f 11 and f 12 . Particularly there has been a problem that it is very difficult to satisfy the conditions for oscillation when the frequency switch width has exceeded 500 MHz. When switching member is provided in the amplification system 13 , in addition to the switching member D 11 provided in the resonance system 12 , it is possible to increase the switch width between the oscillation frequencies f 11 and f 12 . However, in so doing, the number of components increases, miniaturization or cost reduction can not be achieved.

Accordingly, it is an object of the present invention to provide a frequency-switching oscillator in which the switching member does not cause loss in the resonance system, there is no drop in the output level, and no deterioration in the carrier to noise ratio.

Furthermore, it is an object of the present invention to provide a frequency-switching oscillator in which the switch width between oscillation frequencies can easily be increased without increasing the number of components, and which can be miniaturized and made inexpensive. In particular, it is an object of the present invention to provide a frequency-switching oscillator which can easily satisfy conditions for oscillation even when the frequency switch width has exceeded 500 MHz, or more.

In order to achieve the above mentioned objects, the frequency-switching oscillator of the present invention comprises a resonance system and an amplification system, for switching between two or more oscillation frequencies, the amplification system comprising a switching member. The switching member switches between two or more oscillation frequencies by switching the impedance of the amplification system so that the impedance of the amplification system satisfies conditions for oscillation at one of the oscillation frequencies, and does not satisfy the conditions for oscillation at other oscillation frequencies.

Preferably, the switching member changes the value of the feedback capacitance of the amplification system, and changes the frequency characteristics of the negative resistance of the impedance of the amplification system.

Preferably, the output of the frequency-switching oscillator is switched between two or more oscillation frequencies by switching only the impedance of the amplification system.

Preferably, the impedance of the resonance system satisfies the conditions for oscillation at two or more oscillation frequencies.

Preferably, the resonance system has a resonant point between the phase of the impedance of the resonance system at one of the oscillation frequencies, and the phase of the impedance of the resonance system at another of the oscillation frequencies.

Preferably, the resonance system has a phase shift circuit for determining the difference between the phase of the impedance of the resonance system at one of the oscillation frequencies, and the phase of the impedance of the resonance system at another of the oscillation frequencies.

Preferably, the resonance system has a resonance circuit, and the phase shift circuit has a coil and two capacitors. One end of the coil is connected to the resonance circuit, and is grounded via one of the capacitors. The other end of the coil is connected to the amplification system, and is grounded via the other capacitor.

Preferably, the resonance system has a resonance output terminal, and the amplification system has an oscillation input terminal, a switch voltage input terminal, and an oscillation output terminal. The oscillation input terminal is connected to the resonance output terminal, a switch voltage is input to the switch voltage input terminal, and an oscillating signal having two or more oscillation frequencies is output from the oscillation output terminal. The switching member is connected to the switch voltage input terminal, and switches the impedance of the amplification system by the switch voltage.

Preferably, the amplification system has an amplifier element and capacitance member, the amplifier element has a first terminal, a second terminal, and a third terminal. The first terminal is grounded in a high frequency band to be used, the second terminal is connected to the resonance system, and the capacitance member and the switching member are connected in series between the third terminal and the second terminal.

Preferably, the capacitance member is a capacitor, the switching member is a diode, one end of the capacitor is connected to the second terminal, the other end of the capacitor is connected to one end of the diode, the other end of the diode is connected to the third terminal, and the switch voltage input terminal is connected to one end of the diode.

Furthermore, an electronic device according to the present invention uses the frequency-switching oscillator described above.

According to the constitution described above, since the frequency-switching oscillator of the present invention comprises a switching member only in the amplification system, there is no loss caused by the switching member in the resonance system. Accordingly the output level does not decrease, and the carrier to noise ratio is good.

Furthermore, since there is a large phase difference between the impedances of the resonance system at each of the oscillation frequency, the carrier to noise ratio of the oscillation signal is good.

Furthermore, according to the frequency-switching oscillator of the present invention, there is a large phase difference between the impedances of the resonance system at each of the oscillation frequency. Consequently, the conditions for oscillation can easily be satisfied because the switching member is provided in the amplification system, even when the switch width between the oscillation frequencies is wide.

Furthermore, since no switching member is provided in the resonance system even when the switch width between the oscillation frequencies is wide, the number of components can be reduced, miniaturization and cost reduction can be achieved.

Furthermore, since the impedance of the resonance system satisfies the conditions for oscillation at two or more oscillation frequencies, there is no need to provide a switching member in the resonance system. As a consequence, the number of components can be reduced, miniaturization and cost reduction can be achieved.

Furthermore, the phase difference between the impedances of the resonance system can be greatly increased by providing a phase shift circuit in the resonance system. As a result, the conditions for oscillation can be easily satisfied, and the carrier to noise ratio can be improved.

Furthermore, since the electronic device of the present invention uses a frequency-switching oscillator in which the output level does not decrease, the carrier to noise ratio is good, and miniaturization and cost reduction are achieved, the electronic device consequently has similar advantages.

FIG. 1 is a block diagram showing a first embodiment of a frequency-switching oscillator of the present invention;

FIG. 2 is a diagram showing a detailed example of a resonance system of the frequency-switching oscillator of FIG. 1;

FIG. 3 is a diagram showing a detailed example of an amplification system of the frequency-switching oscillator of FIG. 1;

FIGS. 4A and 4B are Smith charts showing impedance of the resonance system of the frequency-switching oscillator of FIG. 1, FIG. 4A showing the impedance at a point a 2 , and FIG. 4B showing the impedance at a point a 2

FIGS. 5A and 5B are Smith charts showing impedance of the amplification system of the frequency-switching oscillator of FIG. 1, FIG. 5A showing the impedance when the diode D 1 is conductive, and FIG. 5B showing the impedance when the diode D 11 is nonconductive;

FIG. 6 is a circuit diagram showing a detailed example of the frequency-switching oscillator of FIG. 1;

FIG. 7 is a block diagram showing an embodiment of an electronic device of the present invention;

FIG. 8 is a Smith chart showing impedance in a resonance system and an amplification system of a frequency-switching oscillator;

FIG. 9 is a circuit diagram showing a conventional frequency-switching oscillator;

FIGS. 10A and 10B are Smith charts showing impedance of the amplification system of the frequency-switching oscillator of FIG. 9, FIG. 10A showing the impedance when the diode D 1 is conductive, and FIG. 10B showing the impedance when the diode D 11 is nonconductive; and

FIG. 11 is a Smith chart showing the impedance of an amplification system in the frequency-switching oscillator of FIG. 9 .

FIG. 1 shows a frequency-switching oscillator according to a first embodiment of the present invention. In FIG. 1, the frequency-switching oscillator 1 has a resonance system 2 and an amplification system 3 . The resonance system 2 has a resonance output terminal a 2 , and the amplification system 3 has an oscillation input terminal a 3 , a switch voltage input terminal a 5 , and an oscillation output terminal a 6 . Furthermore, the resonance output terminal a 2 and the oscillation input terminal a 3 are connected.

In order to output the oscillation signal s 1 at the oscillation frequency of f 1 or f 2 from the oscillation output terminal a 6 , the above frequency-switching oscillator 1 is required to have a constitution in which the resonance system 2 and the amplification system 3 satisfy conditions for oscillation at a plurality of frequencies.

The internal configuration of the resonance system 2 of the frequency-switching oscillator 1 will be explained with reference to FIG. 2, and the impedance of the resonance system 2 viewed from the resonance output terminal a 2 will be explained using FIGS. 4A and 4B. In FIG. 2, the same portions as or equivalent portions to those in FIG. 1 are given the same reference numerals, and explanation thereof is omitted. Furthermore, the reference numerals f 1 and f 2 shown in FIGS. 4A and 4B represent the impedances at the oscillation frequencies f 1 and f 2 respectively. Although the present invention is described herein in terms of oscillation at oscillation frequencies f 1 and f 2 , it will be appreciated that the present invention may be configured to oscillate at more than two oscillation frequencies. That is, the present invention may oscillate at a plurality a plurality of oscillation frequencies.

In FIG. 2, the resonance system 2 has a resonance circuit 4 and a phase shift circuit 5 , and the phase shift circuit 5 has a capacitor C 2 , a coil L 1 , and a capacitor C 3 . One end of the coil L 1 is connected to the resonance circuit 4 , and the other end is connected to the resonance output terminal a 2 . One end of each of the capacitors C 2 and C 3 is grounded. The other ends of capacitors C 2 and C 3 are connected to each respective end of the coil L 1 . Furthermore, the impedance of the resonance system 2 is shown in FIG. 4 A. In FIG. 4A, the impedances at the oscillation frequencies f 1 and f 2 are inductive, and can for instance be used as an inductance element of a Colpitts oscillator. Moreover, there is a large phase difference between the impedances at the oscillation frequencies f 1 and f 2 . Furthermore, there is a resonance point between each of the impedance.

Here, FIG. 4B shows the impedance viewed from the terminal a 2 when the phase shift circuit 5 is removed from the resonance system 2 . In FIG. 4B the impedance at the oscillation frequency f 2 is a capacitive impedance, and does not satisfy the conditions for oscillation of a Colpitts oscillator. Thus, in FIG. 4A, by providing the phase shift circuit 5 in the resonance system 2 , the difference in phase between the impedances is increased, as well as the conditions for oscillation are satisfied. If the impedance viewed from the terminal a 2 when the phase shift circuit 5 is removed from the resonance system 2 in FIG. 4B satisfies the conditions for oscillation, the phase shift circuit 5 need not be provided.

Next, the internal configuration of the amplification system 3 of the frequency-switching oscillator 1 will be explained in detail with reference to FIG. 3, and the impedance of the amplification system 3 viewed from the oscillation input terminal a 3 will be explained using FIGS. 5A and 5B. In FIG. 3, the same portions as or equivalent portions to those in FIG. 1 are given the same reference numerals, and explanation thereof is omitted. Furthermore, reference numerals f 1 and f 2 shown in FIGS. 5A and 5B represent the impedance at the oscillation frequencies f 1 and f 2 .

In FIG. 3, the amplification system 3 has a capacitance member comprising a capacitor C 1 , and a switching member comprising a diode D 1 . Then, the cathode of the diode D 1 , an end of the capacitor C 1 and an end of the switch voltage input terminal a 5 are connected, respectively. The diode D 1 becomes conductive when a switch voltage is not applied to the switch voltage input terminal a 5 , and the diode D 1 becomes nonconductive when a switch voltage is applied to the switch voltage input terminal as. Furthermore, FIGS. 5A and 5B show the impedance of the amplification system 3 . FIG. 5A shows the impedance when a switch voltage is not applied to the switch voltage input terminal a 5 , i.e. diode D 1 is conductive, and FIG. 5B shows the impedance when a switch voltage is applied to the switch voltage input terminal as, i.e. diode D 1 is nonconductive.

When a switch voltage is not applied to the switch voltage input terminal a 5 , at the oscillation frequency f 1 of FIG. 5A, the impedance has sufficient negative resistance to compensate the impedance of the resonance system 2 shown in FIG. 4A, and at the oscillation frequency f 2 of FIG. 5A, the impedance does not have sufficient negative resistance to compensate the impedance of the resonance system 2 of FIG. 4 A. Therefore, the frequency-switching oscillator 1 satisfies the conditions for oscillation at the oscillation frequency f 1 , but does not satisfy the conditions for oscillation at the oscillation frequency f 2 .

On the other hand, when a switch voltage is applied to the switch voltage input terminal a 5 , at the oscillation frequency f 1 of FIG. 5B, the impedance does not have sufficient negative resistance to compensate the impedance of the resonance system 2 shown in FIG. 4A, but at the oscillation frequency f 2 of FIG. 5B, the impedance does have sufficient negative resistance to compensate the impedance of the resonance system 2 of FIG. 4 A. Therefore, the frequency-switching oscillator 1 does not satisfy the conditions for oscillation at the oscillation frequency f 1 , but satisfies the conditions for oscillation at the oscillation frequency f 2 .

Therefore, in the frequency-switching oscillator 1 of the above configuration in which the resonance system 2 and the amplification system 3 are connected, the oscillation signal s 1 is outputted from the oscillation output terminal a 6 . The oscillation signal s 1 has the oscillation frequency of f 1 when the switch voltage is not applied to the switch voltage input terminal a 5 , i.e. the diode D 1 is conductive, and has the oscillation frequency of f 2 when the switch voltage is applied, i.e. the diode D 1 is nonconductive.

FIG. 6 shows a detailed circuit diagram of the frequency-switching oscillator of the present invention shown in FIG. 1 . In FIG. 6, the frequency-switching oscillator 1 has a resonance system 2 and a amplification system 3 . The resonance system 2 has a resonance circuit 4 and a phase shift circuit 5 . The frequency-switching oscillator 1 is a type of voltage-controlled oscillator, and consequently the resonance circuit 4 has a resistor R 1 , a variable-capacitance diode VD 1 , capacitors C 4 and C 5 , and a coil L 2 . One end of the resistor R 1 is connected to a control voltage input terminal al, and the other end is connected to the cathode of the variable-capacitance diode VD 1 . The anode of the variable-capacitance diode VD 1 is grounded. The cathode of the variable-capacitance diode VD 1 is connected via the capacitor C 4 to one end of the coil L 2 , and the other end of the coil L 2 is grounded. Furthermore, one end of the coil L 2 is connected via the capacitor C 5 to the phase shift circuit 5 . The phase shift circuit 5 has a coil L 1 , and capacitors C 2 and C 3 . One end of the coil L 1 is connected to the resonance circuit 4 , and in addition, is grounded via the capacitor C 2 . The other end of the coil L 1 is connected to the amplification system 3 , and is grounded via the capacitor C 3 . As explained above, FIG. 4A shows the impedance of the resonance system 2 , and FIG. 4B shows the impedance at point a 2 when the phase shift circuit 5 is removed from the resonance system 2 .

The amplification system 3 has an amplifier element comprising a transistor TR 1 , the switching member comprising a diode D 1 , the capacitance member comprising a capacitor C 1 , capacitors C 6 , C 7 , C 8 , a coil L 1 , and resistors R 2 , R 3 , R 4 , R 5 , and R 6 . The power supply voltage input terminal a 4 is connected via the coil L 3 to the collector of the transistor TR 1 , and is connected via the resistor R 5 to the base of the transistor TRI. The collector of the transistor TR 1 is grounded in a high frequency band to be used via the capacitor C 6 for grounding. The base of the transistor TRI is connected via the oscillation input terminal a 3 to the resonance system 2 , and is grounded via the resistor R 4 . The emitter of the transistor TR 1 is connected to the anode of the diode D 1 , grounded via the resistor R 6 and the capacitor C 7 , and is connected to the oscillation output terminal a 6 via the capacitor C 8 . The cathode of the diode D 1 is connected via the capacitor C 1 to the base of the transistor TR 1 , grounded via the resistor R 3 , and is connected to the switch voltage input terminal a 5 via the resistor R 2 . In this way, in the specific circuit, when the switching member comprising the diode D 1 is connected to the switch voltage input terminal a 5 , preferably the resistor R 2 for protection should be provided therebetween. Then, the coil L 3 is a choke coil, the capacitor C 6 is a capacitor for grounding, the capacitor C 7 is a capacitance between the emitter and the collector of the transistor TR 1 , and the resistors R 3 , R 4 , R 5 , and R 6 are bias resistances. Then, the oscillation signal s 1 is output from the oscillation output terminal a 6 via the capacitor C 8 .

In the frequency-switching oscillator 1 having such a constitution, the synthetic capacitance is synthesized from the capacitor C 1 , which is the capacitance between the base and the emitter of the transistor TR 1 , and the diode D 1 . The synthetic capacitance greatly contributes to determining the frequency at which the impedance of the amplification system 3 has negative resistance. Then, when a switch voltage is applied to the switch voltage input terminal a 5 , the diode D 1 becomes nonconductive, and the capacitance between the base and emitter of the transistor TR 1 has a value obtained by connecting the capacitance of the capacitor C 1 and the capacitance of the diode D 1 in series. When no switch voltage is applied to the switch voltage input terminal a 5 , the diode D 1 becomes conductive, and the capacitance between the base and emitter of the transistor TR 1 has the value of the capacitance of the capacitor C 1 . As described above, the impedance of the amplification system 3 is shown in FIG. 5A when the diode D 1 is conductive, and is shown in FIG. 5B when the diode D 1 is nonconductive. Then, when the diode D 1 is conductive, the impedance of the amplification system 3 has sufficient negative resistance at the oscillation frequency f 1 to compensate the impedance of the resonance system 2 , and is a resistance at the oscillation frequency f 2 . Furthermore, when the diode D 1 is nonconductive, the impedance is a resistance at the oscillation frequency f 1 , and has sufficient negative resistance at the oscillation frequency f 2 to compensate the impedance of the resonance system 2 .

For example, when the frequency-switching oscillator 1 outputs oscillation frequencies f 1 =892.0 MHz and f 2 =1757.4 MHz, the output level at the frequency f 1 is 3.04 dBm, and the carrier to noise ratio is −121 dBc/Hz. At the frequency f 2 , the output level is 4.3 dBm, and the carrier to noise ratio is −117 dBc/Hz.

Thus, according to the frequency-switching oscillator 1 described above, the resonance system 2 is not provided with the diode D 1 as switching member, and the diode D 1 is provided only in the amplification system 3 . Then, by changing the state of the diode D 1 in the amplification system 3 the frequency at which the impedance of the amplification system 3 have a negative resistance is altered, thereby enabling the oscillation frequency of the oscillation signal s 1 to be switched between f 1 and f 2 .

Furthermore, the frequency-switching oscillator of the present invention may, of course, be an oscillator other than a Colpitts. The output of the frequency-switching oscillator of the present invention may be switched between three or more oscillation frequencies. Furthermore, the resonance circuit 4 and the phase shift circuit 5 may be those shown in the embodiment described above, or they may have another constitution. In the preceding explanation, an NPN transistor was used as the amplification element, but it is acceptable to use a PNP transistor, an FET transistor, or the like. Furthermore, a mechanical switch and a capacitor connected in series or the like may be used as the switching member instead of the diode, the transistor, and the like. Switching member may also be provided in the resonance circuit 4 .

FIG. 7 is a block diagram showing a communications device forming an embodiment of an electronic device according to the present invention. In FIG. 7, a communications device 20 comprises a signal processing circuit 21 , bandpass filters 22 , 26 , 30 , and 34 , amplifiers 23 , 27 , 31 , and 35 , mixers 25 and 33 , a duplexer 28 , an antenna 29 , and frequency-switching oscillators 1 a and 1 b of the present invention. Here, the output of the signal processing circuit 21 is connected in series via the bandpass filter 22 and the amplifier 23 to the mixer 25 . Furthermore, the output of the frequency-switching oscillator 1 a is connected to the mixer 25 . Then, the output of the mixer 25 is connected in series via the bandpass filter 26 and the amplifier 27 to the duplexer 28 . The duplexer 28 is connected to the antenna 29 . Then, the duplexer 28 is connected in series via the bandpass filter 30 and the amplifier 31 to the mixer 33 . The output of the frequency-switching oscillator 1 b also is connected to the mixer 33 . The output of the mixer 33 is connected in series via the bandpass filter 34 and the amplifier 35 to the signal processing circuit 21 .

In the communications device 20 of such a configuration, firstly, during transmission, the signal processing circuit 21 creates an output signal, the bandpass filter 22 removes unwanted signals from this output signal, the amplifier 23 amplifies it, the mixer 25 mixes it with a signal from the frequency-switching oscillator 1 a and a frequency conversion is performed through converting it to an RF signal, the bandpass filter 26 removes unwanted signals from the RF signal, the amplifier 23 amplifies it, and then the signal passes through the duplexer 28 and is radiated from the antenna 29 . Furthermore, during reception, the RF signal received by the antenna 29 passes through the duplexer 28 and is input to the bandpass filter 30 , which removes unwanted signals therefrom, the amplifier 31 amplifies it, the mixer 23 mixes it with a signal from the frequency-switching oscillator 1 b and a frequency conversion is performed through converting it to an IF signal, the bandpass filter 34 removes unwanted signals from the IF signal, the amplifier 35 amplifies it, and then the signal is input to the signal processing circuit 21 . Signals are received and transmitted in this way.

Thus, since the abovementioned communications device 20 uses frequency-switching oscillators 1 a and 1 b according to the present invention, in which switching member do not need to be provided in the resonance system, and consequently, the number of components can be reduced, miniaturization and cost reduction are achieved.

Furthermore, since the communications device 20 having the configuration described above uses the frequency-switching oscillators 1 a and 1 b of the present invention, the output level does not decrease and the carrier to noise ratio is excellent. Consequently a high-performance product can be provided.

An electronic device using the frequency-switching oscillator of the present invention was described above using the communications device 20 , but the electronic device of the present invention is of course not limited to a communications device of this configuration.

Since the frequency-switching oscillator of the present invention is provided with the switching member in the amplification system, but not in the resonance system, there is no loss caused by switching member in the resonance system, no drop in the output level, and a good carrier to noise ratio.

Furthermore, in the frequency-switching oscillator of the present invention, since there is a large phase difference between the impedances at each oscillation frequency, the oscillation signal has a good carrier to noise ratio.

Furthermore, according to the frequency-switching oscillator of the present invention, since there is a large phase difference between the impedances at each oscillation frequency, and the switching member is provided in the amplification system, and therefore, the conditions for oscillation can easily be satisfied even when a switch width between the oscillation frequencies is wide.

Furthermore, in the frequency-switching oscillator of the present invention, since no switching member is provided in the resonance system when a switch width between the oscillation frequencies is wide, the number of components can be reduced, making miniaturization and cost reduction possible.

Furthermore, in the frequency-switching oscillator of the present invention, since the impedance of the resonance system satisfies the conditions for oscillation at two or more oscillation frequencies, there is no need to provide switching member in the resonance system. Consequently, the number of components can be reduced, making miniaturization and cost reduction possible.

Then, in the frequency-switching oscillator of the present invention, by providing a phase shift circuit in the resonance system, the phase difference between the impedances of the resonance system can be greatly increased, whereby the conditions for oscillation can be easily satisfied, and the carrier to noise ratio can be improved.

The electronic device using the frequency-switching oscillator of the present invention achieves similar effects to those described above.